Method for transmitting dmrs in wireless communication system supporting nb-iot and apparatus therefor

ABSTRACT

The present specification relates to a method for transmitting, by a terminal, a demodulation reference signal (DMRS) in a wireless communication system supporting narrow-band (NB)-Internet of things (IOT), the method comprising: generating, for single tone transmission, a reference signal sequence to be used for demodulation; mapping the reference signal sequence to a plurality of symbols; and transmitting, in the plurality of symbols, the demodulation reference signal to a base station by using a single tone, wherein phase rotation is applied to each of the plurality of symbols.

TECHNICAL FIELD

The present invention relates to a wireless communication systemsupporting NarrowBand-Internet of Things (NB-IoT) and, moreparticularly, to a method for transmitting a demodulation referencesignal (DMRS) in a wireless communication system supporting NB-IoT andan apparatus supporting the same.

BACKGROUND ART

Mobile communication systems have been developed to provide voiceservices while ensuring the activity of a user. However, the mobilecommunication systems have been expanded to their regions up to dataservices as well as voice. Today, the shortage of resources is causeddue to an explosive increase of traffic, and more advanced mobilecommunication systems are required due to user's need for higher speedservices.

Requirements for a next-generation mobile communication system basicallyinclude the acceptance of explosive data traffic, a significant increaseof a transfer rate per user, the acceptance of the number ofsignificantly increased connection devices, very low end-to-end latency,and high energy efficiency. To this end, research is carried out onvarious technologies, such as dual connectivity, massive Multiple InputMultiple Output (MIMO), in-band full duplex, Non-Orthogonal MultipleAccess (NOMA), the support of a super wideband, and device networking.

DISCLOSURE Technical Problem

An object of this specification is to provide a method of defining anNB-PUSCH frame structure for supporting single tone transmission in anNB-IoT system.

Specifically, an object of this specification is to provide a method ofdetermining the position of a DMRS symbol for supporting an NB-PUSCH.

Furthermore, an object of this specification is to provide a method ofgenerating a DMRS sequence and applying a phase rotation to each of aDMRS symbol and/or data symbol so as to minimize a PAPR/CM.

Furthermore, an object of this specification is to provide a method ofsetting an initial phase value of a phase rotation.

Furthermore, an object of this specification is to provide a method ofcompensating for the timing offset of DMRS sequences for multipleterminals.

Technical objects to be achieved in this specification are not limitedto the aforementioned objects, and those skilled in the art to which thepresent invention pertains may evidently understand other technologicalobjects from the following description.

Technical Solution

This specification provides a method of transmitting a demodulationreference signal (DMRS) in a wireless communication system supportingNarrowband (NB)-Internet of Things (IoT). The method performed by aterminal includes generating a reference signal sequence used fordemodulation with respect to single tone transmission, mapping areference signal sequence to multiple symbols, and transmitting the DMRSto a base station in the multiple symbols using a single tone. If anarrow band (NB) physical uplink channel is transmitted as the singletone, BPSK or QPSK is applied as a modulation scheme for the NB physicaluplink channel. A phase rotation is applied to each of the multiplesymbols. The applied phase rotation is determined based on a modulationscheme applied to the NB physical uplink channel. The multiple symbolscorrespond to the first symbol, second symbol and third symbol of aslot, respectively.

Furthermore, in this specification, the applied phase rotation isdetermined based on a first parameter determined according to themodulation scheme.

Furthermore, in this specification, the first parameter is π/2 or π/4.

Furthermore, in this specification, the applied phase rotation isdetermined based on the first parameter and a result value of modulooperation of 2 for a symbol index indicative of a symbol within aspecific time unit.

Furthermore, in this specification, the phase rotation is applied toeach of symbols to which the NB physical uplink channel is mapped.

Furthermore, in this specification, the DMRS sequence is generated usinga pseudo-random sequence.

Furthermore, this specification further includes applying orthogonalcover code (OCC) to the multiple symbols.

Furthermore, in this specification, the initial phase value of the phaserotation is applied at the start of each specific unit.

Furthermore, in this specification, the specific unit is a slot,subframe or radio frame.

Furthermore, in this specification, the initial phase value is set usingat least one of a cell ID and the specific unit.

Furthermore, in this specification, the narrow band (NB) has a bandwidthof 180 kHz.

Furthermore, in this specification, the transmission of the DMRS isperformed in an inband mode of the NB-IoT system.

Furthermore, this specification provides a terminal for transmitting ademodulation reference signal (DMRS) in a wireless communication systemsupporting Narrowband (NB)-Internet of Things (IoT). The terminalincludes a radio frequency (RF) unit for transmitting and receivingradio signals and a processor functionally coupled to the RF unit. Theprocessor generates a reference signal sequence used for demodulationwith respect to single tone transmission, maps a reference signalsequence to multiple symbols, and controls to transmit the DMRS to abase station in the multiple symbols using a single tone. If a narrowband (NB) physical uplink channel is transmitted as the single tone,BPSK or QPSK is applied as a modulation scheme for the NB physicaluplink channel. A phase rotation is applied to each of the multiplesymbols. The applied phase rotation is determined based on a modulationscheme applied to the NB physical uplink channel. The multiple symbolscorrespond to the first symbol, second symbol and third symbol of aslot, respectively.

Advantageous Effects

This specification has an effect in that it can avoid a collisionbetween a DMRS of NB-IoT and SRS transmission legacy of LTE bydetermining the position of a DMRS symbol for supporting an NB-PUSCHwith consideration taken of the position of an SRS symbol of legacy LTE.

Furthermore, this specification has an effect in that it can minimize aPAPR/CM that may occur in single tone transmission by generating a DMRSsequence and applying a phase rotation to each of a DMRS symbol and/or adata symbol.

Furthermore, this specification has an effect in that it can reduceinter-cell interference by newly defining the initial phase value of aphase rotation.

Furthermore, this specification has an effect in that it can reduceinter-cell interference by compensating for the timing offset of DMRSsequences for multiple terminals.

Effects which may be obtained by this specification are not limited tothe aforementioned effects, and various other effects may be evidentlyunderstood by those skilled in the art to which the present inventionpertains from the following description.

DESCRIPTION OF DRAWINGS

The accompanying drawings included as part of the detailed descriptionin order to help understanding of the present invention provideembodiments of the present invention and describe the technicalcharacteristics of the present invention along with the detaileddescription.

FIG. 1 illustrates the structure of a wireless frame in a wirelesscommunication system to which the present invention is applicable.

FIG. 2 illustrates a resource grid for one DL slot in a wirelesscommunication system to which the present invention is applicable.

FIG. 3 illustrates the structure of a DL subframe in a wirelesscommunication system to which the present invention is applicable.

FIG. 4 illustrates the structure of an UL subframe in a wirelesscommunication system to which the present invention is applicable.

FIG. 5 illustrates an example of a form in which PUCCH formats aremapped to a PUCCH area of an UL physical resource block in a wirelesscommunication system to which the present invention is applicable.

FIG. 6 illustrates the structure of a CQI channel in the case of ageneral CP in a wireless communication system to which the presentinvention is applicable.

FIG. 7 illustrates the structure of ACK/NACK channel in the case of ageneral CP in a wireless communication system to which the presentinvention is applicable.

FIG. 8 illustrates an example of generating 5 SC-FDMA symbols during oneslot and generating the generated 5 SC-FDMA symbols in a wirelesscommunication system to which the present invention is applicable.

FIG. 9 illustrates an example of a component carrier and a carrieraggregation in a wireless communication system to which the presentinvention is applicable.

FIG. 10 illustrates an example of a subframe structure according to across carrier scheduling in a wireless communication system to which thepresent invention is applicable.

FIG. 11 illustrates an example of a transmission channel processing ofan UL-SCH in a wireless communication system to which the presentinvention is applicable.

FIG. 12 illustrates an example of a signal processing process of an ULshared channel which is a transport channel in a wireless communicationsystem to which the present application is applicable.

FIG. 13 illustrates a reference signal pattern which is mapped on a DLresource block pair in a wireless communication system to which thepresent invention is applicable.

FIG. 14 illustrates an UL subframe including a sounding reference signalsymbol in a wireless communication system to which the present inventionis applicable.

FIG. 15 illustrates an example of a multiplexing of legacy PDCCH, PDSCHand EPDCCH.

FIG. 16 illustrates a section of a cell division of a system supportinga carrier aggregation.

FIG. 17 illustrates the structure of a frame used for SS transmission ina system which uses a basic CP (Cyclic Prefix).

FIG. 18 illustrates a frame structure used for SS transmission in asystem which uses an extended CP.

FIG. 19 illustrates two sequences in a logical region being interleavedand mapped in a physical region.

FIG. 20 illustrates a frame structure in which M-PSS and M-SSS aremapped.

FIG. 21 illustrates a method of generating M-PSS according to anembodiment of the present invention.

FIG. 22 illustrates a method of generating M-SSS according to anembodiment of the present invention.

FIG. 23 illustrates an example of a method of implementing M-PSS towhich a method proposed in the present specification is applicable.

FIG. 24 illustrates how UL numerology is stretched in a time domain.

FIG. 25 illustrates an example of time units for the UL of NB-LTE basedon 2.5 kHz subcarrier spacing.

FIG. 26 illustrates an example of an operation system of NB LTE systemto which the method proposed in the present specification is applicable.

FIG. 27 illustrates an example of an NB-frame structure of 15 kHzsubcarrier spacing to which the method proposed in the presentspecification is applicable.

FIG. 28 illustrates an example of NB-frame structure for 3.75 kHzsubcarrier spacing to which the method proposed in the presentspecification is applicable.

FIG. 29 illustrates an example of NB subframe structure in 3.75 kHzsubcarrier spacing to which the method proposed in the presentspecification is applicable.

FIG. 30 illustrates an example of PUSCH processing in NB-IoT system towhich the method proposed in the present specification is applicable.

FIG. 31 illustrates an example of an LTE turbo encoder used for PUSCH inNB-IoT system to which the method proposed in the present specificationis applicable.

FIG. 32 shows the configuration of a common multi-input and multi-outputantenna (MIMO) communication system.

FIG. 33 is a diagram showing channels from multiple Tx antennas to oneRx antenna.

FIG. 34 shows an example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

FIG. 35 shows another example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

FIG. 36 shows another example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

FIG. 37 shows another example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

FIG. 38 shows another example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

FIG. 39 is a flowchart illustrating an example of a method oftransmitting and receiving DM-RSs in NB-IoT proposed in thisspecification.

FIG. 40 shows an example of the internal block diagram of a wirelesscommunication apparatus to which the methods proposed in thisspecification may be applied.

MODE FOR INVENTION

Hereafter, preferred embodiments of the present invention will bedescribed in detail with reference to the accompanying drawings. Adetailed description to be disclosed hereinafter together with theaccompanying drawing is to describe embodiments of the present inventionand not to describe a unique embodiment for carrying out the presentinvention. The detailed description below includes details in order toprovide a complete understanding. However, those skilled in the art knowthat the present invention can be carried out without the details.

In some cases, in order to prevent a concept of the present inventionfrom being ambiguous, known structures and devices may be omitted or maybe illustrated in a block diagram format based on core function of eachstructure and device.

In the specification, a base station means a terminal node of a networkdirectly performing communication with a terminal. In the presentdocument, specific operations described to be performed by the basestation may be performed by an upper node of the base station in somecases. That is, it is apparent that in the network constituted bymultiple network nodes including the base station, various operationsperformed for communication with the terminal may be performed by thebase station or other network nodes other than the base station. Ingeneral, a base station (BS) may be substituted with a term, such as afixed station, Node B, evolved-NodeB (eNB), base transceiver system(BTS) or access point (AP). Further, a ‘terminal’ may be fixed ormovable and be substituted with a term, such as a user equipment (UE), amobile station (MS), a user terminal (UT), a mobile subscriber station(MSS), a subscriber station (SS), an advanced mobile station (AMS), awireless terminal (WT), a machine-type communication (MTC) device, amachine-to-machine (M2M) device or a device-to-device (D2D) device.

Hereinafter, a downlink means communication from the base station to theterminal and an uplink means communication from the terminal to the basestation. In the downlink, a transmitter may be a part of the basestation and a receiver may be a part of the terminal. In the uplink, thetransmitter may be a part of the terminal and the receiver may be a partof the base station.

Specific terms used in the following description are provided to helpappreciating the present invention and the use of the specific terms maybe modified into other forms within the scope without departing from thetechnical spirit of the present invention.

The following technology may be used in various wireless access systems,such as code division multiple access (CDMA), frequency divisionmultiple access (FDMA), time division multiple access (TDMA), orthogonalfrequency division multiple access (OFDMA), single carrier-FDMA(SC-FDMA), non-orthogonal multiple access (NOMA), and the like. The CDMAmay be implemented by radio technology universal terrestrial radioaccess (UTRA) or CDMA2000. The TDMA may be implemented by radiotechnology such as Global System for mobile communications (GSM)/generalpacket radio service (GPRS)/enhanced data rates for GSM evolution(EDGE). The OFDMA may be implemented as radio technology such as IEEE802.11 (Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802-20, E-UTRA (Evolved UTRA),and the like. The UTRA is a part of a universal mobile telecommunicationsystem (UMTS). 3rd generation partnership project (3GPP) long termevolution (LTE) as a part of an evolved UMTS (E-UMTS) using evolved-UMTSterrestrial radio access (E-UTRA) adopts the OFDMA in a downlink and theSC-FDMA in an uplink. LTE-advanced (A) is an evolution of the 3GPP LTE.

The embodiments of the present invention may be based on standarddocuments disclosed in at least one of IEEE 802, 3GPP, and 3GPP2 whichare the wireless access systems. That is, steps or parts which are notdescribed to definitely show the technical spirit of the presentinvention among the embodiments of the present invention may be based onthe documents. Further, all terms disclosed in the document may bedescribed by the standard document.

3GPP LTE/LTE-A is basically described for clear description, but thetechnical features of the present invention are not limited thereto.

General System

FIG. 1 illustrates a structure a radio frame in a wireless communicationsystem to which the present invention can be applied.

In 3GPP LTE/LTE-A, radio frame structure type 1 may be applied tofrequency division duplex (FDD) and radio frame structure type 2 may beapplied to time division duplex (TDD) are supported.

FIG. 1(a) exemplifies radio frame structure type 1. The radio frame isconstituted by 10 subframes. One subframe is constituted by 2 slots in atime domain. A time required to transmit one subframe is referred to asa transmissions time interval (TTI). For example, the length of onesubframe may be 1 ms and the length of one slot may be 0.5 ms.

One slot includes a plurality of orthogonal frequency divisionmultiplexing (OFDM) symbols in the time domain and includes multipleresource blocks (RBs) in a frequency domain. In 3GPP LTE, since OFDMA isused in downlink, the OFDM symbol is used to express one symbol period.The OFDM symbol may be one SC-FDMA symbol or symbol period. The resourceblock is a resource allocation wise and includes a plurality ofconsecutive subcarriers in one slot.

FIG. 1(b) illustrates frame structure type 2. Radio frame type 2 isconstituted by 2 half frames, each half frame is constituted by 5subframes, a downlink pilot time slot (DwPTS), a guard period (GP), andan uplink pilot time slot (UpPTS), and one subframe among them isconstituted by 2 slots. The DwPTS is used for initial cell discovery,synchronization, or channel estimation in a terminal. The UpPTS is usedfor channel estimation in a base station and to match uplinktransmission synchronization of the terminal. The guard period is aperiod for removing interference which occurs in uplink due tomulti-path delay of a downlink signal between the uplink and thedownlink.

In frame structure type 2 of a TDD system, an uplink-downlinkconfiguration is a rule indicating whether the uplink and the downlinkare allocated (alternatively, reserved) with respect to all subframes.Table 1 shows he uplink-downlink configuration.

TABLE 1 Downlink- to-Uplink Uplink- Switch- Downlink point Subframenumber configuration periodicity 0 1 2 3 4 5 6 7 8 9 0  5 ms D S U U U DS U U U 1  5 ms D S U U D D S U U D 2  5 ms D S U D D D S U D D 3 10 msD S U U U D D D D D 4 10 ms D S U U D D D D D D 5 10 ms D S U D D D D DD D 6  5 ms D S U U U D S U U D

Referring to Table 1, for each sub frame of the radio frame, ‘D’represents a subframe for downlink transmission, ‘U’ represents asubframe for uplink transmission, and ‘S’ represents a special subframeconstituted by three fields such as the DwPTS, the GP, and the UpPTS.The uplink-downlink configuration may be divided into 7 configurationsand the positions and/or the numbers of the downlink subframe, thespecial subframe, and the uplink subframe may vary for eachconfiguration.

A time when the downlink is switched to the uplink or a time when theuplink is switched to the downlink is referred to as a switching point.Switch-point periodicity means a period in which an aspect of the uplinksubframe and the downlink subframe are switched is similarly repeatedand both 5 ms and 10 ms are supported. When the period of thedownlink-uplink switching point is 5 ms, the special subframe S ispresent for each half-frame and when the period of the downlink-uplinkswitching point is 5 ms, the special subframe S is present only in afirst half-frame.

In all configurations, subframes #0 and #5 and the DwPTS are intervalsonly the downlink transmission. The UpPTS and a subframe justsubsequently to the subframe are continuously intervals for the uplinktransmission.

The uplink-downlink configuration may be known by both the base stationand the terminal as system information. The base station transmits onlyan index of configuration information whenever the uplink-downlinkconfiguration information is changed to announce a change of anuplink-downlink allocation state of the radio frame to the terminal.Further, the configuration information as a kind of downlink controlinformation may be transmitted through a physical downlink controlchannel (PDCCH) similarly to other scheduling information and may becommonly transmitted to all terminals in a cell through a broadcastchannel as broadcasting information.

The structure of the radio frame is just one example and the numbersubcarriers included in the radio frame or the number of slots includedin the subframe and the number of OFDM symbols included in the slot maybe variously changed.

FIG. 2 is a diagram illustrating a resource grid for one downlink slotin the wireless communication system to which the present invention canbe applied.

Referring to FIG. 2, one downlink slot includes the plurality of OFDMsymbols in the time domain. Herein, it is exemplarily described that onedownlink slot includes 7 OFDM symbols and one resource block includes 12subcarriers in the frequency domain, but the present invention is notlimited thereto.

Each element on the resource grid is referred to as a resource elementand one resource block includes 12×7 resource elements. The number ofresource blocks included in the downlink slot, NDL is subordinated to adownlink transmission bandwidth.

A structure of the uplink slot may be the same as that of the downlinkslot.

FIG. 3 illustrates a structure of a downlink subframe in the wirelesscommunication system to which the present invention can be applied.

Referring to FIG. 3, a maximum of former three OFDM symbols in the firstslot of the sub frame are a control region to which control channels areallocated and the remaining OFDM symbols are a data region to which aphysical downlink shared channel (PDSCH) is allocated. Examples of thedownlink control channel used in the 3GPP LTE include a Physical ControlFormat Indicator Channel (PCFICH), a Physical Downlink Control Channel(PDCCH), a Physical Hybrid-ARQ Indicator Channel (PHICH), and the like.

The PFCICH is transmitted in the first OFDM symbol of the subframe andtransports information on the number (i.e., the size of the controlregion) of OFDM symbols used for transmitting the control channels inthe subframe. The PHICH which is a response channel to the uplinktransports an Acknowledgement (ACK)/Not-Acknowledgement (NACK) signalfor a hybrid automatic repeat request (HARQ). Control informationtransmitted through a PDCCH is referred to as downlink controlinformation (DCI). The downlink control information includes uplinkresource allocation information, downlink resource allocationinformation, or an uplink transmission (Tx) power control command for apredetermined terminal group.

The PDCCH may transport A resource allocation and transmission format(also referred to as a downlink grant) of a downlink shared channel(DL-SCH), resource allocation information (also referred to as an uplinkgrant) of an uplink shared channel (UL-SCH), paging information in apaging channel (PCH), system information in the DL-SCH, resourceallocation for an upper-layer control message such as a random accessresponse transmitted in the PDSCH, an aggregate of transmission powercontrol commands for individual terminals in the predetermined terminalgroup, a voice over IP (VoIP). A plurality of PDCCHs may be transmittedin the control region and the terminal may monitor the plurality ofPDCCHs. The PDCCH is constituted by one or an aggregate of a pluralityof continuous control channel elements (CCEs). The CCE is a logicalallocation wise used to provide a coding rate depending on a state of aradio channel to the PDCCH. The CCEs correspond to a plurality ofresource element groups. A format of the PDCCH and a bit number ofusable PDCCH are determined according to an association between thenumber of CCEs and the coding rate provided by the CCEs.

The base station determines the PDCCH format according to the DCI to betransmitted and attaches the control information to a cyclic redundancycheck (CRC) to the control information. The CRC is masked with a uniqueidentifier (referred to as a radio network temporary identifier (RNTI))according to an owner or a purpose of the PDCCH. In the case of a PDCCHfor a specific terminal, the unique identifier of the terminal, forexample, a cell-RNTI (C-RNTI) may be masked with the CRC. Alternatively,in the case of a PDCCH for the paging message, a paging indicationidentifier, for example, the CRC may be masked with a paging-RNTI(P-RNTI). In the case of a PDCCH for the system information, in moredetail, a system information block (SIB), the CRC may be masked with asystem information identifier, that is, a system information (SI)-RNTI.The CRC may be masked with a random access (RA)-RNTI in order toindicate the random access response which is a response to transmissionof a random access preamble.

FIG. 4 illustrates a structure of an uplink subframe in the wirelesscommunication system to which the present invention can be applied.

Referring to FIG. 4, the uplink subframe may be divided into the controlregion and the data region in a frequency domain. A physical uplinkcontrol channel (PUCCH) transporting uplink control information isallocated to the control region. A physical uplink shared channel(PUSCH) transporting user data is allocated to the data region. Oneterminal does not simultaneously transmit the PUCCH and the PUSCH inorder to maintain a single carrier characteristic.

A resource block (RB) pair in the subframe is allocated to a PUCCH forone terminal. RBs included in the RB pair occupy different subcarriersin two slots, respectively. The RB pair allocated to the PUCCHfrequency-hops in a slot boundary.

Physical Uplink Control Channel (PUCCH)

The uplink control information (UCI) transmitted through the PUCCH mayinclude a scheduling request (SR), HARQ ACK/NACK information, anddownlink channel measurement information.

The HARQ ACK/NACK information may be generated according to a downlinkdata packet on the PDSCH is successfully decoded. In the existingwireless communication system, 1 bit is transmitted as ACK/NACKinformation with respect to downlink single codeword transmission and 2bits are transmitted as the ACK/NACK information with respect todownlink 2-codeword transmission.

The channel measurement information which designates feedbackinformation associated with a multiple input multiple output (MIMO)technique may include a channel quality indicator (CQI), a precodingmatrix index (PMI), and a rank indicator (RI). The channel measurementinformation may also be collectively expressed as the CQI.

20 bits may be used per subframe for transmitting the CQI.

The PUCCH may be modulated by using binary phase shift keying (BPSK) andquadrature phase shift keying (QPSK) techniques. Control information ofa plurality of terminals may be transmitted through the PUCCH and whencode division multiplexing (CDM) is performed to distinguish signals ofthe respective terminals, a constant amplitude zero autocorrelation(CAZAC) sequence having a length of 12 is primary used. Since the CAZACsequence has a characteristic to maintain a predetermined amplitude inthe time domain and the frequency domain, the CAZAC sequence has aproperty suitable for increasing coverage by decreasing apeak-to-average power ratio (PAPR) or cubic metric (CM) of the terminal.Further, the ACK/NACK information for downlink data transmissionperformed through the PUCCH is covered by using an orthogonal sequenceor an orthogonal cover (OC).

Further, the control information transmitted on the PUCCH may bedistinguished by using a cyclically shifted sequence having differentcyclic shift (CS) values. The cyclically shifted sequence may begenerated by cyclically shifting a base sequence by a specific cyclicshift (CS) amount. The specific CS amount is indicated by the cyclicshift (CS) index. The number of usable cyclic shifts may vary dependingon delay spread of the channel. Various types of sequences may be usedas the base sequence the CAZAC sequence is one example of thecorresponding sequence.

Further, the amount of control information which the terminal maytransmit in one subframe may be determined according to the number(i.e., SC-FDMA symbols other an SC-FDMA symbol used for transmitting areference signal (RS) for coherent detection of the PUCCH) of SC-FDMAsymbols which are usable for transmitting the control information.

In the 3GPP LTE system, the PUCCH is defined as a total of 7 differentformats according to the transmitted control information, a modulationtechnique, the amount of control information, and the like and anattribute of the uplink control information (UCI) transmitted accordingto each PUCCH format may be summarized as shown in Table 2 given below.

TABLE 2 PUCCH Format Uplink Control Information (UCI) Format 1Scheduling Request (SR) (unmodulated waveform) Format 1a 1-bit HARQACK/NACK with/without SR Format 1b 2-bit HARQ ACK/NACK with/without SRFormat 2 CQI (20 coded bits) Format 2 CQI and 1- or 2-bit HARQ ACK/NACK(20 bits) for extended CP only Format 2a CQI and 1-bit HARQ ACK/NACK(20 + 1 coded bits) Format 2b CQI and 2-bit HARQ ACK/NACK (20 + 2 codedbits)

PUCCH format 1 is used for transmitting only the SR. A waveform which isnot modulated is adopted in the case of transmitting only the SR andthis will be described below in detail.

PUCCH format 1a or 1b is used for transmitting the HARQ ACK/NACK. PUCCHformat 1a or 1b may be used when only the HARQ ACK/NACK is transmittedin a predetermined subframe. Alternatively, the HARQ ACK/NACK and the SRmay be transmitted in the same subframe by using PUCCH format 1a or 1b.

PUCCH format 2 is used for transmitting the CQI and PUCCH format 2a or2b is used for transmitting the CQI and the HARQ ACK/NACK.

In the case of an extended CP, PUCCH format 2 may be transmitted fortransmitting the CQI and the HARQ ACK/NACK.

FIG. 5 illustrates one example of a type in which PUCCH formats aremapped to a PUCCH region of an uplink physical resource block in thewireless communication system to which the present invention can beapplied.

In FIG. 5, N_(RB) ^(UL) represents the number of resource blocks in theuplink and 0, 1, . . . , N_(RB) ^(UL)−1 mean numbers of physicalresource blocks. Basically, the PUCCH is mapped to both edges of anuplink frequency block. As illustrated in FIG. 5, PUCCH format 2/2a/2bis mapped to a PUCCH region expressed as m=0, 1 and this may beexpressed in such a manner that PUCCH format 2/2a/2b is mapped toresource blocks positioned at a band edge. Further, both the PUCCHformat 2/2a/2b and the PUCCH format 1/1a/1b may be mixed and mapped to aPUCCH region expressed as m=2. Next, PUCCH format 1/1a/1b may be mappedto a PUCCH region expressed as m=3, 4, and 5. The number (RB) of PUCCHRBs which are usable by PUCCH format 2/2a/2b may be indicated toterminals in the cell by broadcasting signaling.

PUCCH format 2/2a/2b is described. PUCCH format 2/2a/2b is a controlchannel for transmitting channel measurement feedback (CQI, PMI, andRI).

A reporting period of the channel measurement feedbacks (hereinafter,collectively expressed as CQI information) and a frequency wise(alternatively, a frequency resolution) to be measured may be controlledby the base station. In the time domain, periodic and aperiodic CQIreporting may be supported. PUCCH format 2 may be used for only theperiodic reporting and the PUSCH may be used for aperiodic reporting. Inthe case of the aperiodic reporting, the base station may instruct theterminal to transmit a scheduling resource loaded with individual CQIreporting for the uplink data transmission.

FIG. 6 illustrates a structure of a CQI channel in the case of a generalCP in the wireless communication system to which the present inventioncan be applied.

In SC-FDMA symbols 0 to 6 of one slot, SC-FDMA symbols 1 and 5 (secondand sixth symbols) may be used for transmitting a demodulation referencesignal and the CQI information may be transmitted in the residualSC-FDMA symbols. Meanwhile, in the case of the extended CP, one SC-FDMAsymbol (SC-FDMA symbol 3) is used for transmitting the DMRS.

In PUCCH format 2/2a/2b, modulation by the CAZAC sequence is supportedand the CAZAC sequence having the length of 12 is multiplied by aQPSK-modulated symbol. The cyclic shift (CS) of the sequence is changedbetween the symbol and the slot. The orthogonal covering is used withrespect to the DMRS.

The reference signal (DMRS) is loaded on two SC-FDMA symbols separatedfrom each other by 3 SC-FDMA symbols among 7 SC-FDMA symbols included inone slot and the CQI information is loaded on 5 residual SC-FDMAsymbols. Two RSs are used in one slot in order to support a high-speedterminal. Further, the respective terminals are distinguished by usingthe CS sequence. CQI information symbols are modulated and transferredto all SC-FDMA symbols and the SC-FDMA symbol is constituted by onesequence. That is, the terminal modulates and transmits the CQI to eachsequence.

The number of symbols which may be transmitted to one TTI is 10 andmodulation of the CQI information is determined up to QPSK. When QPSKmapping is used for the SC-FDMA symbol, since a CQI value of 2 bits maybe loaded, a CQI value of 10 bits may be loaded on one slot. Therefore,a CQI value of a maximum of 20 bits may be loaded on one subframe. Afrequency domain spread code is used for spreading the CQI informationin the frequency domain.

The CAZAC sequence (for example, ZC sequence) having the length of 12may be used as the frequency domain spread code. CAZAC sequences havingdifferent CS values may be applied to the respective control channels tobe distinguished from each other. IFFT is performed with respect to theCQI information in which the frequency domain is spread.

12 different terminals may be orthogonally multiplexed on the same PUCCHRB by a cyclic shift having 12 equivalent intervals. In the case of ageneral CP, a DMRS sequence on SC-FDMA symbol 1 and 5 (on SC-FDMA symbol3 in the case of the extended CP) is similar to a CQI signal sequence onthe frequency domain, but the modulation of the CQI information is notadopted.

The terminal may be semi-statically configured by upper-layer signalingso as to periodically report different CQI, PMI, and RI types on PUCCHresources indicated as PUCCH resource indexes (n_(PUCCH)^((1,{tilde over (p)})), n_(PUCCH) ^((2,{tilde over (p)})), andn_(PUCCH) ^((3,{tilde over (p)}))). Herein, the PUCCH resource index(n_(PUCCH) ^((2,{tilde over (p)}))) is information indicating the PUCCHregion used for PUCCH format 2/2a/2b and a CS value to be used.

PUCCH Channel Structure

PUCCH formats 1a and 1b are described.

In PUCCH format 1a and 1b, the CAZAC sequence having the length of 12 ismultiplied by a symbol modulated by using a BPSK or QPSK modulationscheme. For example, a result acquired by multiplying a modulated symbold(0) by a CAZAC sequence r(n) (n=0, 1, 2, . . . , N−1) having a lengthof N becomes y(0), y(1), y(2), . . . , y(N−1). y(0), . . . , y(N−1)symbols may be designated as a block of symbols. The modulated symbol ismultiplied by the CAZAC sequence and thereafter, the block-wise spreadusing the orthogonal sequence is adopted.

A Hadamard sequence having a length of 4 is used with respect to generalACK/NACK information and a discrete Fourier transform (DFT) sequencehaving a length of 3 is used with respect to the ACK/NACK informationand the reference signal.

The Hadamard sequence having the length of 2 is used with respect to thereference signal in the case of the extended CP.

FIG. 7 illustrates a structure of an ACK/NACK channel in the case of ageneral CP in the wireless communication system to which the presentinvention can be applied.

In FIG. 7, a PUCCH channel structure for transmitting the HARQ ACK/NACKwithout the CQI is exemplarily illustrated.

The reference signal (DMRS) is loaded on three consecutive SC-FDMAsymbols in a middle part among 7 SC-FDMA symbols and the ACK/NACK signalis loaded on 4 residual SC-FDMA symbols.

Meanwhile, in the case of the extended CP, the RS may be loaded on twoconsecutive symbols in the middle part. The number of and the positionsof symbols used in the RS may vary depending on the control channel andthe numbers and the positions of symbols used in the ACK/NACK signalassociated with the positions of symbols used in the RS may alsocorrespondingly vary depending on the control channel.

Acknowledgment response information (not scrambled status) of 1 bit and2 bits may be expressed as one HARQ ACK/NACK modulated symbol by usingthe BPSK and QPSK modulation techniques, respectively. A positiveacknowledgement response (ACK) may be encoded as ‘1’ and a negativeacknowledgment response (NACK) may be encoded as ‘0’.

When a control signal is transmitted in an allocated band, 2-dimensional(D) spread is adopted in order to increase a multiplexing capacity. Thatis, frequency domain spread and time domain spread are simultaneouslyadopted in order to increase the number of terminals or control channelswhich may be multiplexed.

A frequency domain sequence is used as the base sequence in order tospread the ACK/NACK signal in the frequency domain. A Zadoff-Chu (ZC)sequence which is one of the CAZAC sequences may be used as thefrequency domain sequence. For example, different CSs are applied to theZC sequence which is the base sequence, and as a result, multiplexingdifferent terminals or different control channels may be applied. Thenumber of CS resources supported in an SC-FDMA symbol for PUCCH RBs forHARQ ACK/NACK transmission is set by a cell-specific upper-layersignaling parameter (Δ_(shift) ^(PUCCH)).

The ACK/NACK signal which is frequency-domain spread is spread in thetime domain by using an orthogonal spreading code. As the orthogonalspreading code, a Walsh-Hadamard sequence or DFT sequence may be used.For example, the ACK/NACK signal may be spread by using an orthogonalsequence (w0, w1, w2, and w3) having the length of 4 with respect to 4symbols. Further, the RS is also spread through an orthogonal sequencehaving the length of 3 or 2. This is referred to as orthogonal covering(OC).

Multiple terminals may be multiplexed by a code division multiplexing(CDM) scheme by using the CS resources in the frequency domain and theOC resources in the time domain described above. That is, ACK/NACKinformation and RSs of a lot of terminals may be multiplexed on the samePUCCH RB.

In respect to the time-domain spread CDM, the number of spreading codessupported with respect to the ACK/NACK information is limited by thenumber of RS symbols. That is, since the number of RS transmittingSC-FDMA symbols is smaller than that of ACK/NACK informationtransmitting SC-FDMA symbols, the multiplexing capacity of the RS issmaller than that of the ACK/NACK information.

For example, in the case of the general CP, the ACK/NACK information maybe transmitted in four symbols and not 4 but 3 orthogonal spreadingcodes are used for the ACK/NACK information and the reason is that thenumber of RS transmitting symbols is limited to 3 to use only 3orthogonal spreading codes for the RS.

In the case of the subframe of the general CP, when 3 symbols are usedfor transmitting the RS and 4 symbols are used for transmitting theACK/NACK information in one slot, for example, if 6 CSs in the frequencydomain and 3 orthogonal cover (OC) resources may be used, HARQacknowledgement responses from a total of 18 different terminals may bemultiplexed in one PUCCH RB. In the case of the subframe of the extendedCP, when 2 symbols are used for transmitting the RS and 4 symbols areused for transmitting the ACK/NACK information in one slot, for example,if 6 CSs in the frequency domain and 2 orthogonal cover (OC) resourcesmay be used, the HARQ acknowledgement responses from a total of 12different terminals may be multiplexed in one PUCCH RB.

Next, PUCCH format 1 is described. The scheduling request (SR) istransmitted by a scheme in which the terminal requests scheduling ordoes not request the scheduling. An SR channel reuses an ACK/NACKchannel structure in PUCCH format 1a/1b and is configured by an on-offkeying (OOK) scheme based on an ACK/NACK channel design. In the SRchannel, the reference signal is not transmitted. Therefore, in the caseof the general CP, a sequence having a length of 7 is used and in thecase of the extended CP, a sequence having a length of 6 is used.Different cyclic shifts (CSs) or orthogonal covers (OCs) may beallocated to the SR and the ACK/NACK. That is, the terminal transmitsthe HARQ ACK/NACK through a resource allocated for the SR in order totransmit a positive SR. The terminal transmits the HARQ ACK/NACK througha resource allocated for the ACK/NACK in order to transmit a negativeSR.

Next, an enhanced-PUCCH (e-PUCCH) format is described. An e-PUCCH maycorrespond to PUCCH format 3 of an LTE-A system. A block spreadingtechnique may be applied to ACK/NACK transmission using PUCCH format 3.

The block spreading technique is a scheme that modulates transmission ofthe control signal by using the SC-FDMA scheme unlike the existing PUCCHformat 1 series or 2 series. As illustrated in FIG. 8, a symbol sequencemay be spread and transmitted on the time domain by using an orthogonalcover code (OCC). The control signals of the plurality of terminals maybe multiplexed on the same RB by using the OCC. In the case of PUCCHformat 2 described above, one symbol sequence is transmitted throughoutthe time domain and the control signals of the plurality of terminalsare multiplexed by using the cyclic shift (CS) of the CAZAC sequence,while in the case of a block spreading based on PUCCH format (forexample, PUCCH format 3), one symbol sequence is transmitted throughoutthe frequency domain and the control signals of the plurality ofterminals are multiplexed by using the time domain spreading using theOCC.

FIG. 8 illustrates one example of generating and transmitting 5 SC-FDMAsymbols during one slot in the wireless communication system to whichthe present invention can be applied.

In FIG. 8, an example of generating and transmitting 5 SC-FDMA symbols(i.e., data part) by using an OCC having the length of 5 (alternatively,SF=5) in one symbol sequence during one slot. In this case, two RSsymbols may be used during one slot.

In the example of FIG. 8, the RS symbol may be generated from a CAZACsequence to which a specific cyclic shift value is applied andtransmitted in a type in which a predetermined OCC is applied(alternatively, multiplied) throughout a plurality of RS symbols.Further, in the example of FIG. 8, when it is assumed that 12 modulatedsymbols are used for each OFDM symbol (alternatively, SC-FDMA symbol)and the respective modulated symbols are generated by QPSK, the maximumbit number which may be transmitted in one slot becomes 24 bits (=12×2).Accordingly, the bit number which is transmittable by two slots becomesa total of 48 bits. When a PUCCH channel structure of the blockspreading scheme is used, control information having an extended sizemay be transmitted as compared with the existing PUCCH format 1 seriesand 2 series.

General Carrier Aggregation

A communication environment considered in embodiments of the presentinvention includes multi-carrier supporting environments. That is, amulti-carrier system or a carrier aggregation system used in the presentinvention means a system that aggregates and uses one or more componentcarriers (CCs) having a smaller bandwidth smaller than a target band atthe time of configuring a target wideband in order to support awideband.

In the present invention, multi-carriers mean aggregation of(alternatively, carrier aggregation) of carriers and in this case, theaggregation of the carriers means both aggregation between continuouscarriers and aggregation between non-contiguous carriers. Further, thenumber of component carriers aggregated between the downlink and theuplink may be differently set. A case in which the number of downlinkcomponent carriers (hereinafter, referred to as ‘DL CC’) and the numberof uplink component carriers (hereinafter, referred to as ‘UL CC’) arethe same as each other is referred to as symmetric aggregation and acase in which the number of downlink component carriers and the numberof uplink component carriers are different from each other is referredto as asymmetric aggregation. The carrier aggregation may beinterchangeably used with a term, such as a carrier aggregation, abandwidth aggregation or a spectrum aggregation.

The carrier aggregation configured by combining two or more componentcarriers aims at supporting up to a bandwidth of 100 MHz in the LTE-Asystem. When one or more carriers having the bandwidth than the targetband are combined, the bandwidth of the carriers to be combined may belimited to a bandwidth used in the existing system in order to maintainbackward compatibility with the existing IMT system. For example, theexisting 3GPP LTE system supports bandwidths of 1.4, 3, 5, 10, 15, and20 MHz and a 3GPP LTE-advanced system (i.e., LTE-A) may be configured tosupport a bandwidth larger than 20 MHz by using on the bandwidth forcompatibility with the existing system. Further, the carrier aggregationsystem used in the preset invention may be configured to support thecarrier aggregation by defining a new bandwidth regardless of thebandwidth used in the existing system.

The LTE-A system uses a concept of the cell in order to manage a radioresource.

The carrier aggregation environment may be called a multi-cellenvironment. The cell is defined as a combination of a pair of adownlink resource (DL CC) and an uplink resource (UL CC), but the uplinkresource is not required. Therefore, the cell may be constituted by onlythe downlink resource or both the downlink resource and the uplinkresource. When a specific terminal has only one configured serving cell,the cell may have one DL CC and one UL CC, but when the specificterminal has two or more configured serving cells, the cell has DL CCsas many as the cells and the number of UL CCs may be equal to or smallerthan the number of DL CCs.

Alternatively, contrary to this, the DL CC and the UL CC may beconfigured. That is, when the specific terminal has multiple configuredserving cells, a carrier aggregation environment having UL CCs more thanDL CCs may also be supported. That is, the carrier aggregation may beappreciated as aggregation of two or more cells having different carrierfrequencies (center frequencies). Herein, the described ‘cell’ needs tobe distinguished from a cell as an area covered by the base stationwhich is generally used.

The cell used in the LTE-A system includes a primary cell (PCell) and asecondary cell (SCell). The P cell and the S cell may be used as theserving cell. In a terminal which is in an RRC_CONNECTED state, but doesnot have the configured carrier aggregation or does not support thecarrier aggregation, only one serving constituted by only the P cell ispresent. On the contrary, in a terminal which is in the RRC_CONNECTEDstate and has the configured carrier aggregation, one or more servingcells may be present and the P cell and one or more S cells are includedin all serving cells.

The serving cell (P cell and S cell) may be configured through an RRCparameter. PhysCellId as a physical layer identifier of the cell hasinteger values of 0 to 503. SCellIndex as a short identifier used toidentify the S cell has integer values of 1 to 7. ServCellIndex as ashort identifier used to identify the serving cell (P cell or S cell)has the integer values of 0 to 7. The value of 0 is applied to the Pcell and SCellIndex is previously granted for application to the S cell.That is, a cell having a smallest cell ID (alternatively, cell index) inServCellIndex becomes the P cell.

The P cell means a cell that operates on a primary frequency(alternatively, primary CC). The terminal may be used to perform aninitial connection establishment process or a connectionre-establishment process and may be designated as a cell indicatedduring a handover process. Further, the P cell means a cell whichbecomes the center of control associated communication among servingcells configured in the carrier aggregation environment. That is, theterminal may be allocated with and transmit the PUCCH only in the P cellthereof and use only the P cell to acquire the system information orchange a monitoring procedure. An evolved universal terrestrial radioaccess (E-UTRAN) may change only the P cell for the handover procedureto the terminal supporting the carrier aggregation environment by usingan RRC connection reconfiguration message (RRCConnectionReconfigutaion)message of an upper layer including mobile control information(mobilityControllnfo).

The S cell means a cell that operates on a secondary frequency(alternatively, secondary CC). Only one P cell may be allocated to aspecific terminal and one or more S cells may be allocated to thespecific terminal. The S cell may be configured after RRC connectionestablishment is achieved and used for providing an additional radioresource. The PUCCH is not present in residual cells other than the Pcell, that is, the S cells among the serving cells configured in thecarrier aggregation environment. The E-UTRAN may provide all systeminformation associated with a related cell which is in an RRC_CONNECTEDstate through a dedicated signal at the time of adding the S cells tothe terminal that supports the carrier aggregation environment. A changeof the system information may be controlled by releasing and adding therelated S cell and in this case, the RRC connection reconfiguration(RRCConnectionReconfigutaion) message of the upper layer may be used.The E-UTRAN may perform having different parameters for each terminalrather than broadcasting in the related S cell.

After an initial security activation process starts, the E-UTRAN addsthe S cells to the P cell initially configured during the connectionestablishment process to configure a network including one or more Scells. In the carrier aggregation environment, the P cell and the S cellmay operate as the respective component carriers. In an embodimentdescribed below, the primary component carrier (PCC) may be used as thesame meaning as the P cell and the secondary component carrier (SCC) maybe used as the same meaning as the S cell.

FIG. 9 illustrates examples of a component carrier and carrieraggregation in the wireless communication system to which the presentinvention can be applied.

FIG. 9a illustrates a single carrier structure used in an LTE system.The component carrier includes the DL CC and the UL CC. One componentcarrier may have a frequency range of 20 MHz.

FIG. 9b illustrates a carrier aggregation structure used in the LTEsystem. In the case of FIG. 9b , a case is illustrated, in which threecomponent carriers having a frequency magnitude of 20 MHz are combined.Each of three DL CCs and three UL CCs is provided, but the number of DLCCs and the number of UL CCs are not limited. In the case of carrieraggregation, the terminal may simultaneously monitor three CCs, andreceive downlink signal/data and transmit uplink signal/data.

When N DL CCs are managed in a specific cell, the network may allocate M(MEN) DL CCs to the terminal. In this case, the terminal may monitoronly M limited DL CCs and receive the DL signal. Further, the networkgives L (L≤M≤N) DL CCs to allocate a primary DL CC to the terminal andin this case, UE needs to particularly monitor L DL CCs. Such a schememay be similarly applied even to uplink transmission.

A linkage between a carrier frequency (alternatively, DL CC) of thedownlink resource and a carrier frequency (alternatively, UL CC) of theuplink resource may be indicated by an upper-layer message such as theRRC message or the system information. For example, a combination of theDL resource and the UL resource may be configured by a linkage definedby system information block type 2 (SIB2). In detail, the linkage maymean a mapping relationship between the DL CC in which the PDCCHtransporting a UL grant and a UL CC using the UL grant and mean amapping relationship between the DL CC (alternatively, UL CC) in whichdata for the HARQ is transmitted and the UL CC (alternatively, DL CC) inwhich the HARQ ACK/NACK signal is transmitted.

Cross Carrier Scheduling

In the carrier aggregation system, in terms of scheduling for thecarrier or the serving cell, two types of a self-scheduling method and across carrier scheduling method are provided. The cross carrierscheduling may be called cross component carrier scheduling or crosscell scheduling.

The cross carrier scheduling means transmitting the PDCCH (DL grant) andthe PDSCH to different respective DL CCs or transmitting the PUSCHtransmitted according to the PDCCH (UL grant) transmitted in the DL CCthrough other UL CC other than a UL CC linked with the DL CC receivingthe UL grant.

Whether to perform the cross carrier scheduling may be UE-specificallyactivated or deactivated and semi-statically known for each terminalthrough the upper-layer signaling (for example, RRC signaling).

When the cross carrier scheduling is activated, a carrier indicatorfield (CIF) indicating through which DL/UL CC the PDSCH/PUSCH thePDSCH/PUSCH indicated by the corresponding PDCCH is transmitted isrequired. For example, the PDCCH may allocate the PDSCH resource or thePUSCH resource to one of multiple component carriers by using the CIF.That is, the CIF is set when the PDSCH or PUSCH resource is allocated toone of DL/UL CCs in which the PDCCH on the DL CC is multiply aggregated.In this case, a DCI format of LTE-A Release-8 may extend according tothe CIF. In this case, the set CIF may be fixed to a 3-bit field and theposition of the set CIF may be fixed regardless of the size of the DCIformat. Further, a PDCCH structure (the same coding and the same CCEbased resource mapping) of the LTE-A Release-8 may be reused.

On the contrary, when the PDCCH on the DL CC allocates the PDSCHresource on the same DL CC or allocates the PUSCH resource on a UL CCwhich is singly linked, the CIF is not set. In this case, the same PDCCHstructure (the same coding and the same CCE based resource mapping) andDCI format as the LTE-A Release-8 may be used.

When the cross carrier scheduling is possible, the terminal needs tomonitor PDCCHs for a plurality of DCIs in a control region of amonitoring CC according to a transmission mode and/or a bandwidth foreach CC. Therefore, a configuration and PDCCH monitoring of a searchspace which may support monitoring the PDCCHs for the plurality of DCIsare required.

In the carrier aggregation system, a terminal DL CC aggregate representsan aggregate of DL CCs in which the terminal is scheduled to receive thePDSCH and a terminal UL CC aggregate represents an aggregate of UL CCsin which the terminal is scheduled to transmit the PUSCH. Further, aPDCCH monitoring set represents a set of one or more DL CCs that performthe PDCCH monitoring. The PDCCH monitoring set may be the same as theterminal DL CC set or a subset of the terminal DL CC set. The PDCCHmonitoring set may include at least any one of DL CCs in the terminal DLCC set. Alternatively, the PDCCH monitoring set may be definedseparately regardless of the terminal DL CC set. The DL CCs included inthe PDCCH monitoring set may be configured in such a manner thatself-scheduling for the linked UL CC is continuously available. Theterminal DL CC set, the terminal UL CC set, and the PDCCH monitoring setmay be configured UE-specifically, UE group-specifically, orcell-specifically.

When the cross carrier scheduling is deactivated, the deactivation ofthe cross carrier scheduling means that the PDCCH monitoring setcontinuously means the terminal DL CC set and in this case, anindication such as separate signaling for the PDCCH monitoring set isnot required. However, when the cross carrier scheduling is activated,the PDCCH monitoring set is preferably defined in the terminal DL CCset. That is, the base station transmits the PDCCH through only thePDCCH monitoring set in order to schedule the PDSCH or PUSCH for theterminal.

FIG. 10 illustrates one example of a subframe structure depending oncross carrier scheduling in the wireless communication system to whichthe present invention can be applied.

Referring to FIG. 10, a case is illustrated, in which three DL CCs areassociated with a DL subframe for an LTE-A terminal and DL CC ‘A’ isconfigured as a PDCCH monitoring DL CC. When the CIF is not used, eachDL CC may transmit the PDCCH scheduling the PDSCH thereof without theCIF. On the contrary, when the CIF is used through the upper-layersignaling, only one DL CC ‘A’ may transmit the PDCCH scheduling thePDSCH thereof or the PDSCH of another CC by using the CIF. In this case,DL CC ‘B’ and ‘C’ in which the PDCCH monitoring DL CC is not configureddoes not transmit the PDCCH.

General ACK/NACK Multiplexing Method

In a situation in which the terminal simultaneously needs to transmitmultiple ACKs/NACKs corresponding to multiple data units received froman eNB, an ACK/NACK multiplexing method based on PUCCH resourceselection may be considered in order to maintain a single-frequencycharacteristic of the ACK/NACK signal and reduce ACK/NACK transmissionpower.

Together with ACK/NACK multiplexing, contents of ACK/NACK responses formultiple data units may be identified by combining a PUCCH resource anda resource of QPSK modulation symbols used for actual ACK/NACKtransmission.

For example, when one PUCCH resource may transmit 4 bits and four dataunits may be maximally transmitted, an ACK/NACK result may be identifiedin the eNB as shown in Table 3 given below.

TABLE 3 HARQ-ACK(0), HARQ-ACK(1), HARQ-ACK(2), HARQ-ACK(3) n_(PUCCH) ⁽¹⁾b(0), b(1) ACK, ACK, ACK, ACK n_(PUCCH,1) ⁽¹⁾ 1, 1 ACK, ACK, ACK,NACK/DTX n_(PUCCH,1) ⁽¹⁾ 1, 0 NACK/DTX,NACK/DTX,NACK,DTX n_(PUCCH,2) ⁽¹⁾1, 1 ACK, ACK, NACK/DTX, ACK n_(PUCCH,1) ⁽¹⁾ 1, 0 NACK, DTX, DTX, DTXn_(PUCCH,0) ⁽¹⁾ 1, 0 ACK, ACK, NACK/DTX, NACK/DTX n_(PUCCH,1) ⁽¹⁾ 1, 0ACK, NACK/DTX, ACK, ACK n_(PUCCH,3) ⁽¹⁾ 0, 1 NACK/DTX, NACK/DTX,NACK/DTX, NACK n_(PUCCH,3) ⁽¹⁾ 1, 1 ACK, NACK/DTX, ACK, NACK/DTXn_(PUCCH,2) ⁽¹⁾ 0, 1 ACK, NACK/DTX, NACK/DTX, ACK n_(PUCCH,0) ⁽¹⁾ 0, 1ACK, NACK/DTX, NACK/DTX, NACK/DTX n_(PUCCH,0) ⁽¹⁾ 1, 1 NACK/DTX, ACK,ACK, ACK n_(PUCCH,3) ⁽¹⁾ 0, 1 NACK/DTX, NACK, DTX, DTX n_(PUCCH,1) ⁽¹⁾0, 0 NACK/DTX, ACK, ACK, NACK/DTX n_(PUCCH,2) ⁽¹⁾ 1, 0 NACK/DTX, ACK,NACK/DTX, ACK n_(PUCCH,3) ⁽¹⁾ 1, 0 NACK/DTX, ACK, NACK/DTX, NACK/DTXn_(PUCCH,1) ⁽¹⁾ 0, 1 NACK/DTX, NACK/DTX, ACK, ACK n_(PUCCH,3) ⁽¹⁾ 0, 1NACK/DTX, NACK/DTX, ACK, NACK/DTX n_(PUCCH,2) ⁽¹⁾ 0, 0 NACK/DTX,NACK/DTX, NACK/DTX, ACK n_(PUCCH,3) ⁽¹⁾ 0, 0 DTX, DTX, DTX, DTX N/A N/A

In Table 3, HARQ-ACK(i) represents an ACK/NACK result for an i-th dataunit. In Table 3, discontinuous transmission (DTX) means that there isno data unit to be transmitted for the corresponding HARQ-ACK(i) or thatthe terminal may not detect the data unit corresponding to theHARQ-ACK(i).

According to Table 3, a maximum of four PUCCH resources (n_(PUCCH,0)⁽¹⁾, n_(PUCCH,1) ⁽¹⁾, n_(PUCCH,2) ⁽¹⁾, and n_(PUCCH,3) ⁽¹⁾) are providedand b(0) and b(1) are two bits transmitted by using a selected PUCCH.

For example, when the terminal successfully receives all of four dataunits, the terminal transmits 2 bits (1,1) by using n_(PUCCH,1) ⁽¹⁾.

When the terminal fails to decoding in first and third data units andsucceeds in decoding in second and fourth data units, the terminaltransmits bits (1,0) by using n_(PUCCH,3) ⁽¹⁾.

In ACK/NACK channel selection, when there is at least one ACK, the NACKand the DTX are coupled with each other. The reason is that acombination of the PUCCH resource and the QPSK symbol may not allACK/NACK states. However, when there is no ACK, the DTX is decoupledfrom the NACK.

In this case, the PUCCH resource linked to the data unit correspondingto one definite NACK may also be reserved to transmit signals ofmultiple ACKs/NACKs.

Validation of PDCCH for Semi-Persistent Scheduling

Semi-persistent scheduling (SPS) is a scheduling scheme that allocatesthe resource to the terminal to be persistently maintained during aspecific time interval.

When a predetermined amount of data is transmitted for a specific timelike a voice over Internet protocol (VoIP), since the controlinformation need not be transmitted every data transmission interval forthe resource allocation, the waste of the control information may bereduced by using the SPS scheme. In a so-called semi-persistentscheduling (SPS) method, a time resource domain in which the resourcemay be allocated to the terminal is preferentially allocated.

In this case, in a semi-persistent allocation method, a time resourcedomain allocated to a specific terminal may be configured to haveperiodicity. Then, a frequency resource domain is allocated as necessaryto complete allocation of the time-frequency resource. Allocating thefrequency resource domain may be designated as so-called activation.When the semi-persistent allocation method is used, since the resourceallocation is maintained during a predetermined period by one-timesignaling, the resource need not be repeatedly allocated, and as aresult, signaling overhead may be reduced.

Thereafter, since the resource allocation to the terminal is notrequired, signaling for releasing the frequency resource allocation maybe transmitted from the base station to the terminal. Releasing theallocation of the frequency resource domain may be designated asdeactivation.

In current LTE, in which subframes the SPS is first transmitted/receivedthrough radio resource control (RRC) signaling for the SPS for theuplink and/or downlink is announced to the terminal. That is, the timeresource is preferentially designated among the time and frequencyresources allocated for the SPS through the RRC signaling. In order toannounce a usable subframe, for example, a period and an offset of thesubframe may be announced. However, since the terminal is allocated withonly the time resource domain through the RRC signaling, even though theterminal receives the RRC signaling, the terminal does not immediatelyperform transmission and reception by the SPS and the terminal allocatesthe frequency resource domain as necessary to complete the allocation ofthe time-frequency resource. Allocating the frequency resource domainmay be designated as deactivation and releasing the allocation of thefrequency resource domain may be designated as deactivation.

Therefore, the terminal receives the PDCCH indicating the activation andthereafter, allocate the frequency resource according to RB allocationinformation included in the received PDCCH and applies modulation andcode rate depending on modulation and coding scheme (MCS) information tostart transmission and reception according to the period and the offsetof the subframe allocated through the RRC signaling.

Next, when the terminal receives the PDCCH announcing the deactivationfrom the base station, the terminal stops transmission and reception.When the terminal receives the PDCCH indicating the activation orreactivation after stopping the transmission and reception, the terminalresumes the transmission and reception again with the period and theoffset of the subframe allocated through the RRC signaling by using theRC allocation, the MCS, and the like designated by the PDCCH. That is,the time resource is performed through the RRC signaling, but the signalmay be actually transmitted and received after receiving the PDCCHindicating the activation and reactivation of the SPS and the signaltransmission and reception stop after receiving the PDCCH indicating thedeactivation of the SPS.

When all conditions described below are satisfied, the terminal mayvalidate a PDCCH including an SPS indication. First, a CRC parity bitadded for a PDCCH payload needs to be scrambled with an SPS C-RNTI andsecond, a new data indicator (NDI) field needs to be set to 0. Herein,in the case of DCI formats 2, 2A, 2B, and 2C, the new data indicatorfield indicates one activated transmission block.

In addition, when each field used in the DCI format is set according toTables 4 and 5 given below, the validation is completed. When thevalidation is completed, the terminal recognizes that received DCIinformation is valid SPS activation or deactivation (alternatively,release). On the contrary, when the validation is not completed, theterminal recognizes that a non-matching CRC is included in the receivedDCI format.

Table 4 shows a field for validating the PDCCH indicating the SPSactivation.

TABLE 4 DCI format 0 DCI format 1/1A DCI format 2/2A/2B TPC command forset to ‘00’ N/A N/A scheduled PUSCH Cyclic shift DM RS set to ‘000’ N/AN/A Modulation and coding MSB is set N/A N/A scheme and redundancy to‘0’ version HARQ process number N/A FDD: set to FDD: set to ‘000’ ‘000’TDD: set to ‘0000’ TDD: set to ‘0000’ Modulation and coding N/A MSB isset For the enabled transport scheme to ‘0’ block: MSB is set to ‘0’Redundancy version N/A set to ‘00’ For the enabled transport block: setto ‘00’

Table 5 shows a field for validating the PDCCH indicating the SPSdeactivation (alternatively, release).

TABLE 5 DCI format 0 DCI format 1A TPC command for scheduled set to ‘00’N/A PUSCH Cyclic shift DM RS set to ‘000’ N/A Modulation and codingscheme set to ‘11111’ N/A and redundancy version Resource blockassignment and Set to all ‘1’s N/A hopping resource allocation HARQprocess number N/A FDD: set to ‘000’ TDD: set to ‘0000’ Modulation andcoding scheme N/A set to ‘11111’ Redundancy version N/A set to ‘00’Resource block assignment N/A Set to all ‘1’s

When the DCI format indicates SPS downlink scheduling activation, a TPCcommand value for the PUCCH field may be used as indexes indicating fourPUCCH resource values set by the upper layer.

PUCCH Piggybacking in Rel-8 LTE

FIG. 11 illustrates one example of transport channel processing of aUL-SCH in the wireless communication system to which the presentinvention can be applied.

In a 3GPP LTE system (=E-UTRA, Rel. 8), in the case of the UL, singlecarrier transmission having an excellent peak-to-average power ratio(PAPR) or cubic metric (CM) characteristic which influences theperformance of a power amplifier is maintained for efficient utilizationof the power amplifier of the terminal. That is, in the case oftransmitting the PUSCH of the existing LTE system, data to betransmitted may maintain the single carrier characteristic throughDFT-precoding and in the case of transmitting the PUCCH, information istransmitted while being loaded on a sequence having the single carriercharacteristic to maintain the single carrier characteristic. However,when the data to be DFT-precoded is non-contiguously allocated to afrequency axis or the PUSCH and the PUCCH are simultaneouslytransmitted, the single carrier characteristic deteriorates. Therefore,when the PUSCH is transmitted in the same subframe as the transmissionof the PUCCH as illustrated in FIG. 11, uplink control information (UCI)to be transmitted to the PUCCH is transmitted (piggyback) together withdata through the PUSCH.

Since the PUCCH and the PUSCH may not be simultaneously transmitted asdescribed above, the existing LTE terminal uses a method thatmultiplexes uplink control information (UCI) (CQI/PMI, HARQ-ACK, RI, andthe like) to the PUSCH region in a subframe in which the PUSCH istransmitted.

As one example, when the channel quality indicator (CQI) and/orprecoding matrix indicator (PMI) needs to be transmitted in a subframeallocated to transmit the PUSCH, UL-SCH data and the CQI/PMI aremultiplexed after DFT-spreading to transmit both control information anddata. In this case, the UL-SCH data is rate-matched by considering aCQI/PMI resource. Further, a scheme is used, in which the controlinformation such as the HARQ ACK, the RI, and the like punctures theUL-SCH data to be multiplexed to the PUSCH region.

FIG. 12 illustrates one example of a signal processing process of anuplink share channel of a transport channel in the wirelesscommunication system to which the present invention can be applied.

Herein, the signal processing process of the uplink share channel(hereinafter, referred to as “UL-SCH”) may be applied to one or moretransport channels or control information types.

Referring to FIG. 12, the UL-SCH transfers data to a coding unit in theform of a transport block (TB) once every a transmission time interval(TTI).

A CRC parity bit p₀, p₁, p₂ p₃, . . . , p_(L-1) is attached to a bit ofthe transport block received from the upper layer (S120). In this case,A represents the size of the transport block and L represents the numberof parity bits. Input bits to which the CRC is attached are shown in b₀,b₁, b₂, b₃, . . . , b_(B-1). In this case, B represents the number ofbits of the transport block including the CRC.

b₀, b₁, b₂, b₃, . . . , b_(B-1) is segmented into multiple code blocks(CBs) according to the size of the TB and the CRC is attached tomultiple segmented CBs (S121). Bits after the code block segmentationand the CRC attachment are shown in c_(r0), c_(r1), c_(r2), c_(r3), . .. , c_(r(K) _(r) ₋₁₎. Herein, r represents No. (r=0, . . . , C−1) of thecode block and Kr represents the bit number depending on the code blockr. Further, C represents the total number of code blocks.

Subsequently, channel coding is performed (S122). Output bits after thechannel coding are shown in d_(r0) ^((i)), d_(r1) ^((i)), d_(r2) ^((i)),d_(r3) ^((i)), . . . , d_(r(D) _(r) ₋₁₎ ^((i)). In this case, iindicates an encoded stream index and may have a value of 0, 1, or 2. Drrepresents the number of bits of the i-th encoded stream for the codeblock r. r represents the code block number (r=0, . . . , C−1) and Crepresents the total number of code blocks. Each code block may beencoded by turbo coding.

Subsequently, rate matching is performed (S123). Bits after the ratematching are shown in e_(r0), e_(r1), e_(r2), e_(r3), . . . , c_(r(E)_(r) ₋₁₎. In this case, r represents the code block number (r=0, . . . ,C−1) and C represents the total number of code blocks. Er indicates thenumber of rate-matched bits of the r-th code block.

Subsequently, concatenation among the code blocks is performed again(S124). Bits after the concatenation of the code blocks is performed areshown in f₀, f₁, f₂, f₃, . . . , f_(G-1). In this case, G represents thetotal number of bits encoded for transmission and when the controlinformation is multiplexed with the UL-SCH, the number of bits used fortransmitting the control information is not included.

Meanwhile, when the control information is transmitted in the PUSCH,channel coding of the CQI/PMI, the RI, and the ACK/NACK which are thecontrol information is independently performed (S126, S127, and S128).Since different encoded symbols are allocated for transmitting eachpiece of control information, the respective control information hasdifferent coding rates.

In time division duplex (TDD), as an ACK/NACK feedback mode, two modesof ACK/NACK bundling and ACK/NACK multiplexing are supported by anupper-layer configuration. ACK/NACK information bits for the ACK/NACKbundling are constituted by 1 bit or 2 bits and ACK/NACK informationbits for the ACK/NACK multiplexing are constituted by 1 to 4 bits.

After the concatenation among the code blocks in step S134, encoded bitsf₀, f₁, f₂, f₃, . . . , f_(G-1) of the UL-SCH data and encoded bits q₀,q₁, q₂, q₃, . . . , q_(N) _(L) _(·Q) _(CQI) ₋₁ of the CQI/PMI aremultiplexed (S125). A multiplexed result of the data and the CQI/PMI isshown in g ₀, g ₁, g ₂, g ₃, . . . , g _(H′-1). In this case, g _(i)(i=0, . . . , H′−1) represents a column vector having a length of(Q_(m)·N_(L)) H=(G+N_(L)·Q_(CQI)) and H′=H/(N_(L)·Q_(m)) N_(L) indicatesthe number of layers mapped to a UL-SCH transport block and H representsthe total number of encoded bits allocated to N_(L) transport layersmapped with the transport block for the UL-SCH data and the CQI/PMIinformation.

Subsequently, the multiplexed data and CQI/PMI, a channel encoded RI,and the ACK/NACK are channel-interleaved to generate an output signal(S129).

Reference Signal (RS)

In the wireless communication system, since the data is transmittedthrough the radio channel, the signal may be distorted duringtransmission. In order for the receiver side to accurately receive thedistorted signal, the distortion of the received signal needs to becorrected by using channel information. In order to detect the channelinformation, a signal transmitting method know by both the transmitterside and the receiver side and a method for detecting the channelinformation by using an distortion degree when the signal is transmittedthrough the channel are primarily used. The aforementioned signal isreferred to as a pilot signal or a reference signal (RS).

When the data is transmitted and received by using the MIMO antenna, achannel state between the transmitting antenna and the receiving antennaneed to be detected in order to accurately receive the signal.Therefore, the respective transmitting antennas need to have individualreference signals.

The downlink reference signal includes a common RS (CRS) shared by allterminals in one cell and a dedicated RS (DRS) for a specific terminal.Information for demodulation and channel measurement may be provided byusing the reference signals.

The receiver side (i.e., terminal) measures the channel state from theCRS and feeds back the indicators associated with the channel quality,such as the channel quality indicator (CQI), the precoding matrix index(PMI), and/or the rank indicator (RI) to the transmitting side (i.e.,base station). The CRS is also referred to as a cell-specific RS. On thecontrary, a reference signal associated with a feedback of channel stateinformation (CSI) may be defined as CSI-RS.

The DRS may be transmitted through resource elements when datademodulation on the PDSCH is required. The terminal may receive whetherthe DRS is present through the upper layer and is valid only when thecorresponding PDSCH is mapped. The DRS may be referred to as aUE-specific RS or demodulation RS (DMRS).

FIG. 13 illustrates a reference signal pattern mapped to a downlinkresource block pair in the wireless communication system to which thepresent invention can be applied.

Referring to FIG. 13, as a wise in which the reference signal is mapped,the downlink resource block pair may be expressed by one subframe in thetime domain×12 subcarriers in the frequency domain. That is, oneresource block pair has a length of 14 OFDM symbols in the case of anormal cyclic prefix (CP) (FIG. 13a ) and a length of 12 OFDM symbols inthe case of an extended cyclic prefix (CP) (FIG. 13b ). Resourceelements (REs) represented as ‘0’, ‘1’, ‘2’, and ‘3’ in a resource blocklattice mean the positions of the CRSs of antenna port indexes ‘0’, ‘1’,‘2’, and ‘3’, respectively and resource elements represented as ‘D’means the position of the DRS.

Hereinafter, when the CRS is described in more detail, the CRS is usedto estimate a channel of a physical antenna and distributed in a wholefrequency band as the reference signal which may be commonly received byall terminals positioned in the cell. Further, the CRS may be used todemodulate the channel quality information (CSI) and data.

The CRS is defined as various formats according to an antenna array atthe transmitter side (base station). The 3GPP LTE system (for example,release-8) supports various antenna arrays and a downlink signaltransmitting side has three types of antenna arrays of three singletransmitting antennas, two transmitting antennas, and four transmittingantennas. When the base station uses the single transmitting antenna, areference signal for a single antenna port is arrayed. When the basestation uses two transmitting antennas, reference signals for twotransmitting antenna ports are arrayed by using a time divisionmultiplexing (TDM) scheme and/or a frequency division multiplexing (FDM)scheme. That is, different time resources and/or different frequencyresources are allocated to the reference signals for two antenna portswhich are distinguished from each other.

Moreover, when the base station uses four transmitting antennas,reference signals for four transmitting antenna ports are arrayed byusing the TDM and/or FDM scheme. Channel information measured by adownlink signal receiving side (terminal) may be used to demodulate datatransmitted by using a transmission scheme such as single transmittingantenna transmission, transmission diversity, closed-loop spatialmultiplexing, open-loop spatial multiplexing, or multi-user MIMO.

In the case where the MIMO antenna is supported, when the referencesignal is transmitted from a specific antenna port, the reference signalis transmitted to the positions of specific resource elements accordingto a pattern of the reference signal and not transmitted to thepositions of the specific resource elements for another antenna port.That is, reference signals among different antennas are not duplicatedwith each other.

A rule of mapping the CRS to the resource block is defined as below.

$\begin{matrix}{{k = {{6\; m} + {\left( {v + v_{shift}} \right){mod}\; 6}}}{l = \left\{ {{{\begin{matrix}{0,{N_{symb}^{DL} - 3}} & {{{if}\mspace{14mu} p} \in \left\{ {0,1} \right\}} \\1 & {{{if}\mspace{14mu} p} \in \left\{ {2,3} \right\}}\end{matrix}m} = 0},{1\ldots}\mspace{14mu},{{{2 \cdot {ND}_{RB}^{DL}} - {1m^{\prime}}} = {{m + N_{RB}^{\max,{DL}} - {N_{RB}^{DL}v}} = \left\{ {{\begin{matrix}0 & {{{if}\mspace{14mu} p} = {{0\mspace{14mu} {and}\mspace{14mu} l} = 0}} \\3 & {{{if}\mspace{14mu} p} = {{0\mspace{14mu} {and}\mspace{14mu} l} \neq 0}} \\3 & {{{if}\mspace{14mu} p} = {{1\mspace{14mu} {and}\mspace{14mu} l} = 0}} \\0 & {{{if}\mspace{14mu} p} = {{1\mspace{14mu} {and}\mspace{14mu} l} \neq 0}} \\{3\left( {n_{s}{mod}\; 2} \right)} & {{{if}\mspace{14mu} p} = 2} \\{3 + {3\left( {n_{s}{mod}\; 2} \right)}} & {{{if}\mspace{14mu} p} = 3}\end{matrix}v_{shift}} = {N_{ID}^{cell}{mod}\; 6}} \right.}}} \right.}} & \left\lbrack {{Equation}\mspace{14mu} 1} \right\rbrack\end{matrix}$

In Equation 1, k and l represent the subcarrier index and the symbolindex, respectively and p represents the antenna port. N_(symb) ^(DL)represents the number of OFDM symbols in one downlink slot and N_(RB)^(DL) represents the number of radio resources allocated to thedownlink. ns represents a slot index and, N_(ID) ^(cell) represents acell ID. mod represents an modulo operation. The position of thereference signal varies depending on the v_(shift) value in thefrequency domain. Since v_(shift) is subordinated to the cell ID, theposition of the reference signal has various frequency shift valuesaccording to the cell.

In more detail, the position of the CRS may be shifted in the frequencydomain according to the cell in order to improve channel estimationperformance through the CRS. For example, when the reference signal ispositioned at an interval of three subcarriers, reference signals in onecell are allocated to a 3k-th subcarrier and a reference signal inanother cell is allocated to a 3k+1-th subcarrier. In terms of oneantenna port, the reference signals are arrayed at an interval of sixresource elements in the frequency domain and separated from a referencesignal allocated to another antenna port at an interval of threeresource elements.

In the time domain, the reference signals are arrayed at a constantinterval from symbol index 0 of each slot. The time interval is defineddifferently according to a cyclic shift length. In the case of thenormal cyclic shift, the reference signal is positioned at symbolindexes 0 and 4 of the slot and in the case of the extended CP, thereference signal is positioned at symbol indexes 0 and 3 of the slot. Areference signal for an antenna port having a maximum value between twoantenna ports is defined in one OFDM symbol. Therefore, in the case oftransmission of four transmitting antennas, reference signals forreference signal antenna ports 0 and 1 are positioned at symbol indexes0 and 4 (symbol indexes 0 and 3 in the case of the extended CP) andreference signals for antenna ports 2 and 3 are positioned at symbolindex 1 of the slot. The positions of the reference signals for antennaports 2 and 3 in the frequency domain are exchanged with each other in asecond slot.

Hereinafter, when the DRS is described in more detail, the DRS is usedfor demodulating data. A precoding weight used for a specific terminalin the MIMO antenna transmission is used without a change in order toestimate a channel associated with and corresponding to a transmissionchannel transmitted in each transmitting antenna when the terminalreceives the reference signal.

The 3GPP LTE system (for example, release-8) supports a maximum of fourtransmitting antennas and a DRS for rank 1 beamforming is defined. TheDRS for the rank 1 beamforming also means a reference signal for antennaport index 5.

A rule of mapping the DRS to the resource block is defined as below.Equation 2 shows the case of the normal CP and Equation 3 shows the caseof the extended CP.

$\begin{matrix}{{k = {{\left( k^{\prime} \right){mod}\; N_{sc}^{RB}} + {N_{sc}^{RB} \cdot n_{PRB}}}}{k^{\prime} = \left\{ {{\begin{matrix}{{4m^{\prime}} + v_{shift}} & {{{if}\mspace{14mu} l} \in \left\{ {2,3} \right\}} \\{{4m^{\prime}} + {\left( {2 + v_{shift}} \right){mod}\; 4}} & {{{if}\mspace{14mu} l} \in \left\{ {5,6} \right\}}\end{matrix}l} = \left\{ {{\begin{matrix}3 & {l^{\prime} = 0} \\6 & {l^{\prime} = 1} \\2 & {l^{\prime} = 2} \\5 & {l^{\prime} = 3}\end{matrix}l^{\prime}} = \left\{ {{{\begin{matrix}{0,1} & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 0} \\{2,3} & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 1}\end{matrix}m^{\prime}} = 0},1,\ldots \mspace{14mu},{{{3N_{RB}^{PDSCH}} - {1v_{shift}}} = {N_{ID}^{cell}{mod}\; 3}}} \right.} \right.} \right.}} & \left\lbrack {{Equation}\mspace{14mu} 2} \right\rbrack \\{{k = {{\left( k^{\prime} \right){mod}\; N_{sc}^{RB}} + {N_{sc}^{RB} \cdot n_{PRB}}}}{k^{\prime} = \left\{ {{\begin{matrix}{{3m^{\prime}} + v_{shift}} & {{{if}\mspace{14mu} l} = 4} \\{{3m^{\prime}} + {\left( {2 + v_{shift}} \right){mod}\; 3}} & {{{if}\mspace{14mu} l} = 1}\end{matrix}l} = \left\{ {{\begin{matrix}4 & {l^{\prime} \in \left\{ 0.2 \right\}} \\1 & {l^{\prime} = 1}\end{matrix}l^{\prime}} = \left\{ {{{\begin{matrix}0 & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 0} \\{1,2} & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 1}\end{matrix}m^{\prime}} = 0},1,\ldots \mspace{14mu},{{{4N_{RB}^{PDSCH}} - {1v_{shift}}} = {N_{ID}^{cell}{mod}\; 3}}} \right.} \right.} \right.}} & \left\lbrack {{Equation}\mspace{14mu} 3} \right\rbrack\end{matrix}$

In Equations 2 and 3, k and l represent the subcarrier index and thesymbol index, respectively and p represents the antenna port. N_(sc)^(RB) represents the size of the resource block in the frequency domainand is expressed as the number of subcarriers. n_(PRB) represents thenumber of physical resource blocks. N_(RB) ^(PDSCH) represents afrequency band of the resource block for the PDSCH transmission. nsrepresents the slot index and N_(ID) ^(cell) represents the cell ID. modrepresents the modulo operation. The position of the reference signalvaries depending on the v_(shift) value in the frequency domain. Sincev_(shift) is subordinated to the cell ID, the position of the referencesignal has various frequency shift values according to the cell.

Sounding Reference Signal (SRS)

The SRS is primarily used for the channel quality measurement in orderto perform frequency-selective scheduling and is not associated withtransmission of the uplink data and/or control information. However, theSRS is not limited thereto and the SRS may be used for various otherpurposes for supporting improvement of power control and variousstart-up functions of terminals which have not been scheduled. Oneexample of the start-up function may include an initial modulation andcoding scheme (MCS), initial power control for data transmission, timingadvance, and frequency semi-selective scheduling. In this case, thefrequency semi-selective scheduling means scheduling that selectivelyallocates the frequency resource to the first slot of the subframe andallocates the frequency resource by pseudo-randomly hopping to anotherfrequency in the second slot.

Further, the SRS may be used for measuring the downlink channel qualityon the assumption that the radio channels between the uplink and thedownlink are reciprocal. The assumption is valid particularly in thetime division duplex in which the uplink and the downlink share the samefrequency spectrum and are divided in the time domain.

Subframes of the SRS transmitted by any terminal in the cell may beexpressed by a cell-specific broadcasting signal. A 4-bit cell-specific‘srsSubframeConfiguration’ parameter represents 15 available subframearrays in which the SRS may be transmitted through each radio frame. Bythe arrays, flexibility for adjustment of the SRS overhead is providedaccording to a deployment scenario.

A 16-th array among them completely turns off a switch of the SRS in thecell and is suitable primarily for a serving cell that serves high-speedterminals.

FIG. 14 illustrates an uplink subframe including a sounding referencesignal symbol in the wireless communication system to which the presentinvention can be applied.

Referring to FIG. 14, the SRS is continuously transmitted through a lastSC FDMA symbol on the arrayed subframes. Therefore, the SRS and the DMRSare positioned at different SC-FDMA symbols.

The PUSCH data transmission is not permitted in a specific SC-FDMAsymbol for the SRS transmission and consequently, when sounding overheadis highest, that is, even when the SRS symbol is included in allsubframes, the sounding overhead does not exceed approximately 7%.

Each SRS symbol is generated by a base sequence (random sequence or asequence set based on Zadoff-Ch (ZC)) associated with a given time wiseand a given frequency band and all terminals in the same cell use thesame base sequence. In this case, SRS transmissions from a plurality ofterminals in the same cell in the same frequency band and at the sametime are orthogonal to each other by different cyclic shifts of the basesequence to be distinguished from each other.

SRS sequences from different cells may be distinguished by allocatingdifferent base sequences to respective cells, but orthogonality amongdifferent base sequences is not assured.

Coordinated Multi-Point Transmission and Reception (COMP)

According to a demand of LTE-advanced, CoMP transmission is proposed inorder to improve the performance of the system. The CoMP is also calledco-MIMO, collaborative MIMO, network MIMO, and the like. It isanticipated that the CoMP will improves the performance of the terminalpositioned at a cell edge and improve an average throughput of the cell(sector).

In general, inter-cell interference decreases the performance and theaverage cell (sector) efficiency of the terminal positioned at the celledge in a multi-cell environment in which a frequency reuse index is 1.In order to alleviate the inter-cell interference, the LTE system adoptsa simple passive method such as fractional frequency reuse (FFR) in theLTE system so that the terminal positioned at the cell edge hasappropriate performance efficiency in an interference-limitedenvironment. However, a method that reuses the inter-cell interferenceor alleviates the inter-cell interference as a signal (desired signal)which the terminal needs to receive is more preferable instead ofreduction of the use of the frequency resource for each cell. The CoMPtransmission scheme may be adopted in order to achieve theaforementioned object.

The CoMP scheme which may be applied to the downlink may be classifiedinto a joint processing (JP) scheme and a coordinatedscheduling/beamforming (CS/CB) scheme.

In the JP scheme, the data may be used at each point (base station) in aCoMP wise. The CoMP wise means a set of base stations used in the CoMPscheme. The JP scheme may be again classified into a joint transmissionscheme and a dynamic cell selection scheme.

The joint transmission scheme means a scheme in which the signal issimultaneously transmitted through a plurality of points which are allor fractional points in the CoMP wise. That is, data transmitted to asingle terminal may be simultaneously transmitted from a plurality oftransmission points. Through the joint transmission scheme, the qualityof the signal transmitted to the terminal may be improved regardless ofcoherently or non-coherently and interference with another terminal maybe actively removed.

The dynamic cell selection scheme means a scheme in which the signal istransmitted from the single point through the PDSCH in the CoMP wise.That is, data transmitted to the single terminal at a specific time istransmitted from the single point and data is not transmitted to theterminal at another point in the CoMP wise. The point that transmits thedata to the terminal may be dynamically selected.

According to the CS/CB scheme, the CoMP wise performs beamformingthrough coordination for transmitting the data to the single terminal.That is, the data is transmitted to the terminal only in the servingcell, but user scheduling/beamforming may be determined throughcoordination of a plurality of cells in the CoMP wise.

In the case of the uplink, CoMP reception means receiving the signaltransmitted by the coordination among a plurality of points which aregeographically separated. The CoMP scheme which may be applied to theuplink may be classified into a joint reception (JR) scheme and thecoordinated scheduling/beamforming (CS/CB) scheme.

The JR scheme means a scheme in which the plurality of points which areall or fractional points receives the signal transmitted through thePDSCH in the CoMP wise. In the CS/CB scheme, only the single pointreceives the signal transmitted through the PDSCH, but the userscheduling/beamforming may be determined through the coordination of theplurality of cells in the CoMP wise.

Cross-CC Scheduling and E-PDCCH Scheduling

In the existing 3GPP LTE Rel-10 system, if a cross-CC schedulingoperation is defined in an aggregation situation for a plurality of CCs(component carrier=(serving) cell), one CC may be preset to be able toreceive DL/UL scheduling from only one specific CC (i.e., scheduling CC)(namely, to be able to receive DL/UL grant PDCCH for the correspondingscheduled CC).

The corresponding scheduling CC may basically perform a DL/UL schedulingfor the scheduling CC itself.

In other words, the SS for the PDCCH scheduling the scheduling/scheduledCC in the cross-CC scheduling relation may come to exist in the controlchannel area of the scheduling CC.

Meanwhile, in the LTE system, CFDD DL carrier or TDD DL subframes usefirst n OFDM symbols of the subframe for PDCCH, PHICH, PCFICH and thelike which are physical channels for transmission of various pieces ofcontrol information and use the rest of the OFDM symbols for PDSCHtransmission.

At this time, the number of symbols used for control channeltransmission in each subframe is dynamically transmitted to the UEthrough the physical channel such as PCFICH or is semi-staticallytransmitted to the UE through RRC signaling.

At this time, particularly, value n may be set by 1 to 4 symbolsdepending on the subframe characteristic and system characteristic(FDD/TDD, system bandwidth, etc.).

Meanwhile, in the existing LTE system, PDCCH, which is the physicalchannel for transmitting DL/UL scheduling and various controlinformation, may be transmitted through limited OFDM symbols.

Hence, the enhanced PDCCH (i.e., E-PDCCH), which is more freelymultiplexed in PDSCH and FDM/TDM scheme, may be introduced instead ofthe control channel which is transmitted through the OFDM which isseparated from the PDSCH like PDCCH.

FIG. 15 illustrates an example of multiplexing legacy PDCCH, PDSCH andE-PDCCH.

Here, the legacy PDCCH may be expressed as L-PDCCH.

FIG. 16 is a diagram illustrating a cell classification in a system thatsupports the carrier aggregation.

Referring to FIG. 16, a configured cell is a cell that should becarrier-merged based on a measurement report among the cells of a BS maybe configured for each terminal. The configured cell may reserve aresource for an ACK/NACK transmission for a PDSCH transmissionbeforehand. An activated cell is a cell that is configured to transmitPDSCH/PUSCH actually among the configured cells, and performs a ChannelState Information (CSI) report for the PDSCH/PUSCH transmission and aSounding Reference Signal (SRS) transmission. A de-activated cell is acell that does not transmit the PDSCH/PUSCH transmission by a command ofBS or a timer operation, may also stop the CSI report and the SRStransmission.

Synchronization Signal/Sequence (SS)

An SS includes a primary (P)-SS and a secondary (S)-SS, and correspondsto a signal used when a cell search is performed.

FIG. 17 is a diagram illustrating a frame structure used for an SStransmission in a system that uses a normal cyclic prefix (CP). FIG. 10is a diagram illustrating a frame structure used for an SS transmissionin a system that uses an extended CP.

The SS is transmitted in 0th subframe and second slot of the fifthsubframe, respectively, considering 4.6 ms which is a Global System forMobile communications (GSM) frame length for the easiness of aninter-Radio Access Technology (RAT) measurement, and a boundary for thecorresponding radio frame may be detected through the S-SS. The P-SS istransmitted in the last OFDM symbol of the corresponding slot and theS-SS is transmitted in the previous OFDM symbol of the P-SS.

The SS may transmit total 504 physical cell IDs through the combinationof 3 P-SSs and 168 S-SSs. In addition, the SS and the PBCH aretransmitted within 6 RBs at the center of a system bandwidth such that aterminal may detect or decode them regardless of the transmissionbandwidth.

A transmission diversity scheme of the SS is to use a single antennaport only and not separately used in a standard. That is, thetransmission diversity scheme of the SS uses a single antennatransmission or a transmission technique transparent to a terminal(e.g., Precoder Vector Switching (PVS), Time-Switched Transmit Diversity(TSTD) and Cyclic-Delay Diversity (CDD)).

1. P-SS Sign

Zadoff-Chu (ZC) sequence of length 63 in frequency domain may be definedand used as a sequence of the P-SS. The ZC sequence is defined byEquation 4, a sequence element, n=31 that corresponds to a DC subcarrieris punctured. In Equation 4, N_zc=63.

$\begin{matrix}{{d_{u}(n)} = e^{{- j}\frac{\pi \; {{un}{({n + 1})}}}{N_{ZC}}}} & \left\lbrack {{Equation}\mspace{14mu} 4} \right\rbrack\end{matrix}$

Among 6 RBs (=7 subcarriers) positioned at the center of frequencydomain, the remaining 9 subcarriers are always transmitted in zerovalue, which makes it easy to design a filter for performingsynchronization. In order to define total three P-SSs, the value ofu=29, 29 and 34 may be used in Equation 4. In this case, since 29 and 34have the conjugate symmetry relation, two correlations may besimultaneously performed. Here, the conjugate symmetry means Equation 5.By using the characteristics, it is possible to implement one shotcorrelator for u=29 and 43, and accordingly, about 33.3% of total amountof calculation may be decreased.

d _(u)(n)=(−1)^(n)(d _(N) _(ZC) _(-u)(n))*, when N _(ZC) is even number.

d _(u)(n)=(d _(N) _(ZC) _(-u)(n))*, when N _(ZC) is oddnumber.  [Equation 5]

2. S-SS Sign

The sequence used for the S-SS is combined with two interleavedm-sequences of length 31, and 168 cell group IDs are transmitted bycombining two sequences. The m-sequence as the SSS sequence is robust inthe frequency selective environment, and may be transformed to thehigh-speed m-sequence using the Fast Hadamard Transform, thereby theamount of operations being decreased. In addition, the configuration ofSSS using two short codes is proposed to decrease the amount ofoperations of terminal.

FIG. 19 is a diagram illustrating two sequences in a logical regionbeing mapped to a physical region by being interleaved.

Referring to FIG. 19, when two m-sequences used for generating the S-SSsign are defined by S1 and S2, in the case that the S-SS (S1, S2) ofsubframe 0 transmits the cell group ID with the combination, the S-SS(S2, S1) of subframe 5 is transmitted with being swapped, therebydistinguishing the 10 ms frame boundary. In this case, the SSS sign usesthe generation polynomial x5+x2+1, and total 31 signs may be generatedthrough the circular shift.

In order to improve the reception performance, two different P-SS-basedsequences are defined and scrambled to the S-SS, and scrambled to S1 andS2 with different sequences. Later, by defining the S1-based scramblingsign, the scrambling is performed to S2. In this case, the sign of S-SSis exchanged in a unit of 5 ms, but the P-SS-based scrambling sign isnot exchanged. The P-SS-based scrambling sign is defined by six circularshift versions according to the P-SS index in the m-sequence generatedfrom the generation polynomial x5+x2+1, and the S1-based scrambling signis defined by eight circular shift versions according to the S1 index inthe m-sequence generated from the generation polynomial x5+x4+x2+x1+1.

The contents below exemplify an asynchronous standard of the LTE system.

-   -   A terminal may monitor a downlink link quality based on a        cell-specific reference signal in order to detect a downlink        radio link quality of PCell.    -   A terminal may estimate a downlink radio link quality for the        purpose of monitoring the downlink radio link quality of PCell,        and may compare it with Q_out and Q_in, which are thresholds.    -   The threshold value Q_out may be defined as a level in which a        downlink radio link is not certainly received, and may        correspond to a block error rate 10% of a hypothetical PDCCH        transmission considering a PCFICH together with transmission        parameters.    -   The threshold value Q_in may be defined as a downlink radio link        quality level, which may be great and more certainly received        than Q_out, and may correspond to a block error rate 2% of a        hypothetical PDCCH transmission considering a PCFICH together        with transmission parameters.

Narrow Band (NB) LTE Cell Search

In the NB-LTE, although a cell search may follow the same rule as theLTE, there may be an appropriate modification in the sequence design inorder to increase the cell search capability.

FIG. 20 is a diagram illustrating a frame structure to which M-PSS andM-SSS are mapped. In the present disclosure, an M-PSS designates theP-SS in the NB-LTE, and an M-SSS designates the S-SS in the NB-LTE. TheM-PSS may also be designated to ‘NB-PSS’ and the M-SSS may also bedesignated to ‘NB-SSS’.

Referring to FIG. 20, in the case of the M-PSS, a single primarysynchronization sequence/signal may be used. (M-)PSS may be spanned upto 9 OFDM symbol lengths, and used for determining subframe timing aswell as an accurate frequency offset.

This may be interpreted that a terminal may use the M-PSS for acquiringtime and frequency synchronization with a BS. In this case, (M-)PSS maybe consecutively located in time domain.

The M-SSS may be spanned up to 6 OFDM symbol lengths, and used fordetermining the timing of a cell identifier and an M-frame. This may beinterpreted that a terminal may use the M-SSS for detecting anidentifier of a BS. In order to support the same number as the number ofcell identifier groups of the LTE, 504 different (M-)SSS may bedesigned.

Referring to the design of FIG. 20, the M-PSS and the M-SSS are repeatedevery 20 ms average, and existed/generated four times in a block of 80ms. In the subframes that include synchronization sequences, the M-PSSoccupies the last 9 OFDM symbols. The M-SSS occupies 6th, 7th, 10th,11th, 13th and 14th OFDM symbols in the case of normal CP, and occupies5th, 6th, 9th, 11th and 12th OFDM symbols in the case of extended CP.

The 9 OFDM symbols occupied by the M-PSS may be selected to support forthe in-band disposition between LTE carriers. This is because the firstthree OFDM symbols are used to carry a PDCCH in the hosting LTE systemand a subframe includes minimum twelve OFDM symbols (in the case ofextended CP).

In the hosting LTE system, a cell-specific reference signal (CRS) istransmitted, and the resource elements that correspond to the M-PSS maybe punctured in order to avoid a collision. In the NB-LTE, a specificposition of M-PSS/M-SSS may be determined to avoid a collision with manylegacy LTE signals such as the PDCCH, the PCFICH, the PHICH and/or theMBSFN.

In comparison with the LTE, the synchronization sequence design in theNB-LTE may be different.

This may be performed in order to attain a compromise between decreasedmemory consumption and faster synchronization in a terminal. Since theM-SSS is repeated four times in 80 ms duration, a slight designmodification for the M-SSS may be required in the 80 ms duration inorder to solve a timing uncertainty.

Structure of M-PSS and M-SSS

In the LTE, the PSS structure allows the low complexity design of timingand frequency offset measuring instrument, and the SSS is designed toacquire frame timing and to support unique 504 cell identifiers.

In the case of In-band and Guard-band of the LTE, the disposition of CPin the NB-LTE may be selected to match the CP in a hosting system. Inthe case of standalone, the extended CP may be used for matching atransmitter pulse shape for exerting the minimum damage to the hostingsystem (e.g., GSM).

A single M-PSS may be clearly stated in the N-LTE of the LTE. In theprocedure of PSS synchronization of the LTE, for each of PSSs, aspecific number of frequency speculations may be used for the coarseestimation of symbol timing and frequency offset.

Such an adaption of the procedure in the NB-LTE may increase the processcomplexity of a receiver according to the use of a plurality offrequency assumptions. In order to solve the problem, a sequenceresembling of the Zadoff-Chu sequence which is differentially decoded intime domain may be proposed for the M-PSS. Since the differentialdecoding is performed in a transmission process, the differentialdecoding may be performed during the processing time of a receiver.Consequently, a frequency offset may be transformed from the consecutiverotation for symbols to the fixed phase offset with respect to thecorresponding symbols.

FIG. 21 is a diagram illustrating a method for generating M-PSSaccording to an embodiment of the present invention.

Referring to FIG. 21, first, when starting with a basic sequence oflength 107 as a basis in order to generate an M-PSS, Equation 6 belowmay be obtained.

$\begin{matrix}{{{c(n)} = e^{- \frac{j\; \pi \; {{un}{({n + 1})}}}{N}}},{n = \left\{ {0,1,2,\ldots \mspace{14mu},106} \right\}}} & \left\lbrack {{Equation}\mspace{14mu} 6} \right\rbrack\end{matrix}$

The basic sequence c(n) may be differentially decoded in order to obtaind(n) sequence as represented in Equation 7.

d(n+1)=d(n)c(n), n={0,1,2, . . . ,106}, d(0)=1,  [Equation 7]

The d(n) sequence is divided into 9 sub sequences, and each sub sequencehas a length 12 and a sampling rate of 130 kHz. The 120-point FFT isperformed for each of 9 sub sequences, and each sequence may beoversampled 128/12 times up to 1.92 MHz sampling rate using 128 IFFTzero padding. Consequently, each sub sequence may be mapped to 12subcarriers for 9 OFDM symbols, respectively.

Each of the sub sequences is mapped to a single OFDM symbol, and theM-PSS may occupy total 9 OFDM symbols since total 9 sub sequences areexisted. Total length of the M-PSS may be 1234(=(128+9)*9+1) when thenormal CP of 9 samples are used, and may be 1440 when the extended CP isused.

The M-PSS which is going to be actually used during the transmission isnot required to be generated every time using complex procedure in atransmitter/receiver in the same manner. The complexity coefficient(i.e., t_u(n)) that corresponds to the M-PSS may be generated inoffline, and directly stored in the transmitter/receiver. In addition,even in the case that the M-PSS is generated in 1.92 MHz, the occupationbandwidth may be 180 kHz.

Accordingly, in the case of performing the procedure related to time andfrequency offset measurements using the M-PSS in a receiver, thesampling rate of 192 kHz may be used for all cases. This maysignificantly decrease the complexity of receiver in the cell search.

In comparison with the LTE, the frequency in which the M-PSS isgenerated in the NB-LTE causes slightly greater overhead than the PSS inthe LTE. More particularly, the synchronization sequence used in the LTEoccupies 2.86% of the entire transmission resources, and thesynchronization sequence used in the NB-LTE occupies about 5.36% of theentire transmission resources. Such an additional overhead has an effectof decreasing memory consumption as well as the synchronization timethat leads to the improved battery life and the lower device price.

The M-SSS is designed in frequency domain and occupies 12 subcarriers ineach of 6 OFDM symbols. Accordingly, the number of resource elementsdedicated to the M-SSS may be 72. The M-SSS includes the ZC sequence ofa single length 61 which are padded by eleven ‘0’s on the startingpoint.

In the case of the extended CP, the first 12 symbols of the M-SSS may bediscarded, and the remaining symbols may be mapped to the valid OFDMsymbols, which cause to discard only a single symbol among the sequenceof length 61 since eleven ‘0’s are existed on the starting point. Thediscard of the symbol causes the slight degradation of the correlationproperty of other SSS.

The cyclic shift of a sequence and the sequence for different roots mayeasily provide specific cell identifiers up to 504. The reason why theZC sequence is used in the NB-LTE in comparison with the LTE is todecrease the error detection rate. Since a common sequence for twodifferent cell identifier groups is existed, an additional procedure isrequired in the LTE.

Since the M-PSS/M-SSS occur four times within the block of 80 ms, theLTE design of the SSS cannot be used for providing accurate timinginformation within the corresponding block. This is because the specialinterleaving structure that may determine only two positions.Accordingly, a scrambling sequence may be used in an upper part of theZC sequence in order to provide the information of frame timing. Fourscrambling sequences may be required to determine four positions withinthe block of 80 ms, which may influence on acquiring the accuratetiming.

FIG. 22 is a diagram illustrating a method for generating M-SSSaccording to an embodiment of the present invention.

Referring to FIG. 22, the M-SSS may be defined ass_p,q(n)=a_p(n)·b_q(n). Herein, p={0, 1, . . . , 503} represents cellidentifiers and q={0, 1, 2, 3} determines the position of the M-SSS(i.e., the number of M-SSS within the block of 80 ms which is generatedbefore the latest SSS). In addition, a_p(n) and b_q(n) may be determinedby Equations 8 and 9 below.

                                 [Equation  8] $\begin{matrix}{{{a_{p}(n)} = 0},} & {{n = {\left\{ {{0 - 4},{66 - 71}} \right\} }}} \\{{= {a_{p}\left( {n - k_{p} - 5} \right)}},} & {{n = {\left\{ {5,6,\ldots \mspace{14mu},65} \right\} }}} \\{{{a_{p}(n)} = e^{- \frac{j\; \pi \; {n{(p)}}{n{({n + 1})}}}{61}}},} & {{n = {\left\{ {0,1,\ldots \mspace{14mu},61} \right\} }}}\end{matrix}\mspace{574mu}\left\lbrack {{Equation}\mspace{14mu} 9} \right\rbrack$$\begin{matrix}{{b_{q}(n)} = {b\left( {{mod}\left( {{n - l_{q}},63} \right)} \right)}} & {{{n = \left\{ {0,1,{\ldots \mspace{14mu} 60}} \right\}},{q = \left\{ {0,1,2,3} \right\}},}} \\ & {{{l_{0} = 0},{l_{1} = 3},{l_{2} = 7},{l_{3} = {11}}}}\end{matrix}$b(n + 6) = mod(b(n) + b(n + 1), 2), n = {0, 1, …  55},b(0) = 1, b(m) = 0, m = {1, 2, 3, 4, 5}

Referring to Equation 8, a_p(n) is the ZC sequence and determines a cellidentifier group. m(p) and cyclic shift k_p may be used for providing aspecific cell identifier. Referring to Equation 9, b_q(n) may be thescrambling sequence that includes a cyclic shift of the basic sequenceb_(n), and may be used for indicating the position of the M-SSS in theM-frame in order to acquire the frame timing. The cyclic shift I_q maybe determined according to the value q.

The value of m(p) with respect to the specific p may be determined suchas m(p)=1+mod(p, 61), the value of k_p may be determined such ask_p=7[p/61].

FIG. 23 illustrates an example of a method for implementing M-PSS towhich the method proposed in the present disclosure can be applied.

Particularly, FIG. 23 shows a method for generating an M-PSS using acomplementary Golay sequence.

As shown in FIG. 23, using a complementary Golay sequence pair, a CGSthat is going to be transmitted to each OFDM symbol is selected (i.e.,select a(n) or b(n)).

Next, in the case of using a cover code, c(1) to c(N) may be multipliedto each CGS, and in the case of not using the cover code, 1 may beinputted to all of c(n).

Subsequently, the DFT and the IFFT are performed for each symbol, andtransmitted to each OFDM symbol on time domain.

Additionally, the ZC sequence of length 12 may also generate a sequencethat is going to be transmitted to each OFDM symbol.

In this case, by using the same method applied in FIG. 23, the M-PSS maybe implemented.

NB (Narrow Band)-LTE System

Hereinafter, NB-LTE (or NB-IoT) system will be described.

The UL of NB-LTE is based on SC-FDMA, and this is a special case ofSC-FDMA and may flexibly allocate the bandwidth of the UE includingsingle tone transmission.

One important aspect for the UL SC-FDMA is to enable time of a multipleof co-scheduled UEs coincide with each other so that the arrival timedifference in the base station to be within the cyclic prefix (CP).

Ideally, the UL 15 kHz subcarrier spacing should be used in NB-LTE, butthe time-accuracy, which may be achieved when detecting PRACH from theUEs in a very poor coverage condition, should be considered.

Hence, CP duration needs to be increased.

One way to achieve the above purpose is to reduce the subcarrier spacingfor NB-LTE M-PUSCH to 2.5 kHz by dividing 15 kHz subcarrier spacing by6.

Another motive for reducing subcarrier spacing is to allow a usermultiplexing of a high level.

For example, one user is basically allocated to one subcarrier.

This is more effective for UEs in a condition that the coverage is verylimited like UEs having no benefit from allocation of a high bandwidthwhile the capacity increases due to the simultaneous use of the maximumTX power of a multiple of UEs.

SC-FDMA is used for transmission of a multiple of tones in order tosupport a higher data rate along with the additional PAPR reductiontechnology.

The UL NB-LTE includes 3 basic channels including M-PRACH, M-PUCCH andM-PUSCH.

The design of M-PUCCH discuses at least three alternative plans asfollows.

-   -   One tone in each edge of the system bandwidth    -   UL control information transmission on M-PRACH or M-PUSCH    -   Not having dedicated UL control channel

Time-Domain Frame and Structure

In the UL of NB-LTE having 2.5 kHz subcarrier spacing, the wirelessframe and the subframe are defined as 60 ms and 6 ms, respectively.

As in the DL of NB-LTE, M-frame and M-subframe are defined in the samemanner in the UL link of the NB-LTE.

FIG. 24 illustrates how the UL numerology is stretched in the timedomain.

The NB-LTE carrier includes 5 PRBs in the frequency domain. Each NB-LTEPRB includes 12 subcarriers.

The UL frame structure based on 2.5 kHz subcarrier spacing isillustrated in FIG. 17.

FIG. 24 illustrates an example of UL numerology which is stretched inthe time domain when the subcarrier spacing is reduced from 15 kHz to2.5 kHz.

FIG. 25 illustrates an example of time units for the UL of NB-LTE basedon the 2.5 kHz subcarrier spacing.

Operation System of NB-LTE System

FIG. 26 illustrates an example of an operation system of NB-LTE systemto which the method proposed in the present specification is applicable.

Specifically, FIG. 26(a) illustrates an in-band system, FIG. 26(b)illustrates a guard-band system, and FIG. 26(c) illustrates astand-alone system.

The in-band system may be expressed as an in-band mode, the guard-bandsystem may be expressed as a guard-band mode, and the stand-alone systemmay be expressed as a stand-alone mode.

The in-band system of FIG. 26(a) indicates a system or mode which uses aspecific 1 RB within the legacy LTE band for NB-LTE (or LTE-NB) and maybe operated by allocating some resource blocks of the LTE systemcarrier.

The guard-band system of FIG. 25(b) indicates a system or mode whichuses NB-LTE in the space which is reserved for the guard band of thelegacy LTE band and may be operated by allocating the guard-band of LTEcarrier which is not used as the resource block in the LTE system.

The legacy LTE band includes the minimum 100 kHz at the last of each LTEband.

In order to use 200 kHz, 2 non-continuous guardbands may be used.

The in-band system and the guard-band system indicate the structurewhere NB-LTE co-exists within the legacy LTE band.

In contrast, the standalone system of FIG. 0.26(c) indicates a system ormode which is independently configured from the legacy LTE band and maybe operated by separately allocating the frequency band (futurereallocated GSM carrier) which is used in the GERAN.

FIG. 27 illustrates an example of an NB-frame structure of 15 kHzsubcarrier spacing to which the method proposed in the presentspecification is applicable.

As illustrated in FIG. 27, it may be understood that the NB-framestructure for 15 kHz subcarrier spacing is the same as the framestructure of the legacy system (LTE system).

Namely, 10 ms NB-frame includes 10 1 ms NB-subframes, and 1 msNB-subframe includes 2 0.5 ms NB-slots.

Further, 0.5 ms NB-slot includes 7 OFDM symbols.

FIG. 28 illustrates an example of NB-frame structure for 3.75 kHzsubcarrier spacing to which the method proposed in the presentspecification is applicable.

Referring to FIG. 28, 10 ms NB-frame includes 5 2 ms NB-subframes, and 2ms NB-subframe includes 7 OFDM symbols one guard-period (GP).

The 2 ms NB-subframe may also be expressed as NB-slot or NB-RU (resourceunit), etc.

FIG. 29 illustrates an example of NB subframe structure in 3.75 kHzsubcarrier spacing to which the method proposed in the presentspecification is applicable.

FIG. 29 shows the correspondence between legacy LTE subframe structureand 3.75 subframe structure.

Referring to FIG. 29, subframe (2 ms) of 3.75 kHz corresponds to 2 1 mssubframes (or 1 ms TTIs) of the legacy LTE.

UL Processing Chain

In the NB LTE system, the single tone transmission is used for M-PUSCH(or NPUSCH) in order to minimize PAPR, and as a result, the coverage isimproved.

A specific procedure of the M-PUSCH processing is described withreference to FIG. 30.

FIG. 30 illustrates an example of PUSCH processing in NB-IoT system towhich the method proposed in the present specification is applicable.

FIG. 31 illustrates an example of an LTE turbo encoder used for PUSCH inNB-IoT system to which the method proposed in the present specificationis applicable.

CRC generation of M-PUSCH uses a polynomial which is the same as apolynomial for generating the CRC of M-PDSCH.

In the NB LTE system, the channel coding of the M-PUSCH is based on theLTE turbo code encoder as illustrated in FIG. 31.

The interleaving and the rate matching are the same as the method ofM-PDSCH.

Encoded bits after the rate matching are scrambled with the scramblingmask which is generated according to the RNTI associated with theM-M-PUSCH transmission.

The scrambled codeword is modulated with BPSK or QPSK according to Table6 below.

Table 6 shows an example of BPSK modulation mapping.

TABLE 6 b(i) I Q 0 1 0 1 −1 0

The modulated symbols are grouped in the subcarriers allocated to theM-PUSCH.

In the case of the single tone transmission, the transform precodingblock of FIG. 19 is omitted and the group of MF tones is directed by thebase station. The MF may be 1, 2, 4, or 8.

If only one tone is directed from the base station (i.e., MF=1), the onedirected tone is used for M-PUSCH transmission.

Otherwise, if a multitude of tones are directed from the base station,each set of log 2MF+log 2MQ bits is determined through the tonetransmitted between MF tones and the combination of modulation symbols.

Here, the MQ corresponds the modulation order, and the value is 2 in theBPSK and the value is 4 in the QPSK.

With respect to the SC-FDMA transmission having a multiple of continuoussubcarriers within one cluster, the transform precoding block of FIG. 30is applied to each group in order to obtain frequency-domain symbols(known as SC-FDMA).

In addition, in order to further lower PAPR for BPSK/QPSK, additionallypotential PAPR reduction technologies may be applied.

An example of PAPR reduction technologies is to apply an additionalprecoding filter of M×L dimension (M>L) to the filer of the L×L DFTprecoding.

Thereafter, the first baseband time-continuous signal is generated basedon frequency-domain symbols as in equation 10 below.

$\begin{matrix}{{s_{l}(t)} = {\sum\limits_{k = {{- M}/2}}^{{M/2} - 1}{a_{k,l} \cdot e^{j\; 2{\pi {({k + {1/2}})}}\Delta \; {f{({t - {N_{{CP},l}T_{s}}})}}}}}} & \left\lbrack {{Equation}\mspace{14mu} 10} \right\rbrack\end{matrix}$

With respect to 0≤t<(N_(CP,l)+N)×T_(s) of Equation 10, M means thenumber of subcarriers allocated to M-PUSCH, N=128, Δf=2.5 kHz T_(s)=1/320000, and a_(k,l) means the frequency-domain symbol of thesubcarrier corresponding to k+M/2.

Table 7 below shows values of N_(CP,l) used.

In a special case that M=1, the first baseband time-continuous signal isgenerated based on frequency-domain symbols as Equation 10 below.

s _(l)(t)=a _(0,l) ·e ^(−jπΔf(t-N) ^(CP,l) ^(T) ^(s) ⁾  [Equation 11]

Table 7 shows an example of CUL CP length.

TABLE 7 Configuration Cyclic prefix length N_(CP,l) Normal cyclic prefix10 for l = 0 9 for l = 1,2, . . . ,6

In the above Equations 10 and 11, Δf means a subcarrier spacing andT_(s) means the sampling time.

Multi-Input Multi-Output (MIMO)

In general, the MIMO technology uses multiple transmit (Tx) antennas andmultiple receive (Rx) antennas instead of one Tx antenna and one Rxantenna used so far. In other words, the MIMO technology is a technologyfor attempting a capacity increase or performance improvements usingMIMO antennas in the transmission stage or reception stage of a wirelesscommunication system. Hereinafter, “MIMO” is called “multi-inputmulti-output antennas.”

More specifically, the multi-input multi-output technology does notdepend on one antenna path so as to receive one total message, andcompletes total data by collecting a plurality of data pieces receivedthrough several antennas. As a result, the multi-input multi-outputtechnology can increase the data transfer rate within a specific systemrange and can also increase a system range through a specific datatransfer rate.

It is expected that next-generation mobile communication essentiallyrequires an efficiency multi-input multi-output technology because itrequires a much higher data transfer rate than the existing mobilecommunication. In such a condition, the MIMO communication technology isa next-generation mobile communication technology which may be widelyused in mobile communication terminals, relays, etc. and attractsattention as a technology capable of overcoming a transmission amountlimit to other mobile communication attributable to limited conditionsdue to data communication extension, etc.

Meanwhile, the multi-input multi-output (MIMO) antenna technology ofvarious transmission efficiency improvement technologies that are beingdeveloped has come to the fore as a method capable of significantlyimproving the communication capacity and transmission and receptionperformance even without additional frequency allocation or powerincrease.

FIG. 32 shows the configuration of a common multi-input and multi-outputantenna (MIMO) communication system.

Referring to FIG. 32, if the number of Tx antennas is increased to N_(T)and the number of Rx antennas is increased to N_(R) at the same time, atheoretical channel transmission capacity is increased in proportion tothe number of antennas unlike in a case where multiple antennas are usedin a transmitter or receiver. Accordingly, the transfer rate can beimproved and frequency efficiency can be significantly enhanced. In thiscase, the transfer rate according to an increase of the channeltransmission capacity may be theoretically increased by a value in whicha maximum transfer rate R_(o) when one antenna is used by the followingrate increment R_(i).

R _(i)=min(N _(T) ,N _(R))  [Equation 12]

That is, for example, in a MIMO communication system using four Txantennas and four Rx antennas, a four-times transfer rate can beobtained theoretically compared to a single antenna system.

The technology of such multi-input multi-output antennas may be dividedinto a spatial diversity method of increasing transmission reliabilityusing symbols passing through various channel paths and a spatialmultiplexing method of improving the transfer rate by transmittingmultiple data symbols at the same time using multiple Tx antennas.Furthermore, a method of properly obtaining the advantages by properlycombining the two methods is recently actively researched.

Each of the method is described below more specifically.

First, the spatial diversity method includes a time-space blockcode-series method and a time-space Trelis code-series method using adiversity gain and a coding gain at the same time. In general, theTrelis code method is excellent in bit error rate improvementperformance and the degree of freedom of generation of code, but thetime-space block code is simple in computational complexity. Such aspace diversity gain may be obtained as an amount corresponding to theproduct (NT×NR) of the number of Tx antennas (NT) and the number of Rxantenna (NR).

Second, the spatial multiplexing scheme is a method of transmittingdifferent data streams in Tx antennas. In this case, in a receiver,mutual interference occurs between data transmitted by transmitters atthe same time. The receiver receives data after cancelling suchinterference using a proper signal processing scheme. A noisecancellation method used in this case includes a maximum likelihooddetection (MLD) receiver, a zero-forcing (ZF) receiver, a minimum meansquare error (MMSE) receiver, diagonal-Bell Laboratories layeredspace-time (D-BLAST), vertical-Bell Laboratories layered space-time(V-BLAST), etc. In particular, if a transmission stage is aware ofchannel information, a singular value decomposition (SVD) method, etc.is used.

Third, there is a scheme in which spatial diversity and spatialmultiplexing are combined. If only a spatial diversity gain is obtained,a performance improvement gain according to an increase of diversitydimension is gradually saturated. If only a spatial multiplexing gain isobtained, transmission reliability in a radio channel is deteriorated.Methods for obtaining the two gains while solving the problems have beenresearched. From among, there are methods, such as time-space block code(Double-STTD), time-space BICM (STBICM), etc.

In order to describe the aforementioned communication method in themulti-input multi-output antenna system using a more detailed method,this may be expressed as follows by modeling it mathematically.

First, as shown in FIG. 32, it is assumed that N_(T) Tx antennas andN_(R)Rx antennas are present.

First, a transmission signal is described. As described above, if theN_(T) Tx antennas are present, maximum transmittable information isN_(T), and this may be indicated using the following vector.

S=└S ₁ ,S ₂ , . . . ,S _(N) _(T) ┘^(T)  [Equation 13]

Meanwhile, transmit power may be different in the pieces of transmissioninformation s₁, s₂, . . . , S_(NT). In this case, if the pieces oftransmit power are P₁, P₂, . . . , P_(NT), transmission informationhaving adjusted transmit power may be indicated using the followingvector.

Ŝ=└

,

, . . . ,

┘ ^(T) =└P ₁ s ₁ ,P ₂ s ₂ , . . . ,P _(N) _(T) s _(N) _(T)┘^(T)  [Equation 14]

Furthermore, Ŝ may be expressed as the diagonal matrix P of transmitpower as following.

$\begin{matrix}{\hat{s} = {{\begin{bmatrix}P_{1} & \ldots & 0 \\\vdots & \ddots & \vdots \\0 & \ldots & P_{N_{T}}\end{bmatrix}\begin{bmatrix}s_{1} \\\vdots \\s_{N_{T}}\end{bmatrix}} = {Ps}}} & \left\lbrack {{Equation}\mspace{14mu} 15} \right\rbrack\end{matrix}$

Meanwhile, the information vector Ŝ having adjusted transmit power isthereafter multiplexed by a weight matrix W, forming N_(T) transmissionsignals x₁, x₂, . . . , x_(NT) that are actually transmitted. In thiscase, the weight matrix functions to properly distribute transmissioninformation to each antenna based on a transmission channel condition,etc. Such transmission signals x₁, x₂, . . . , x_(NT) may be expressedusing a vector x as follows.

$\begin{matrix}{X = {\begin{bmatrix}x_{1} \\\vdots \\x_{N_{T}}\end{bmatrix} = {{\begin{bmatrix}w_{11} & \ldots & w_{1N_{T}} \\\vdots & \ddots & \vdots \\w_{N_{T}1} & \ldots & W_{N_{T}N_{T}}\end{bmatrix}\begin{bmatrix}{\hat{s}}_{1} \\\vdots \\{\hat{s}}_{N_{T}}\end{bmatrix}} = {{W\hat{s}} = {WPs}}}}} & \left\lbrack {{Equation}\mspace{14mu} 16} \right\rbrack\end{matrix}$

In this case, w_(ij) indicates a weight between an i-th Tx antenna andj-th transmission information. W indicates the weight in a matrix form.Such a matrix W is called a weight matrix or a precoding matrix.

Meanwhile, the aforementioned transmission signal x may be considered tobe divided into a case where spatial diversity is used and a case wherespace multiplexing is used.

In the case where space multiplexing is used, different signals aremultiplexed and transmitted, and thus all the elements of theinformation vector s have different values. In contrast, if spatialdiversity is used, all the elements of the information vector s have thesame value because the same signal is transmitted through severalchannel paths.

Of course, a method of mixing space multiplexing and spatial diversitymay also be taken into consideration. That is, for example, a case wherethe same signal is transmitted through 3 Tx antennas using spatialdiversity and the remaining different signals are space-multiplexed andtransmitted may also be taken into consideration.

Next, if the N_(R) Rx antennas are present, received signals y₁, y₂, . .. , y_(NR) of the respective antennas are expressed in the form of avector y as follows.

y=└y ₁ ,y ₂ , . . . ,y _(N) _(R) ┘^(T)  [Equation 17]

Meanwhile, if a channel is modeled in a multi-input multi-output antennacommunication system, each channel may be divided depending on a Tx/Rxantenna index. A channel via an Rx antenna i from a Tx antenna j isexpressed as h_(ij). In this case, it is to be noted that in thesequence of indices of h_(ij), the index of an Rx antenna first comesand the index of a Tx antenna comes next.

Such some channels may be grouped and expressed in a vector and matrixform. An example of a vector expression is described below.

FIG. 33 is a diagram showing channels from multiple Tx antennas to oneRx antenna.

As shown in FIG. 33, channels from a total of N_(T) Tx antennas to an Rxantenna i may be expressed as follows.

h _(i) ^(T) =└h _(i1) ,h _(i2) , . . . ,h _(iN) _(T) ┘  [Equation 18]

Furthermore, a case where all of channels via the N_(R) Rx antennas fromthe N_(T) Tx antennas through a matrix expression, such as Equation 18,may be expressed as follows.

$\begin{matrix}{H = {\begin{bmatrix}h_{1}^{T} \\\vdots \\h_{N_{R}}^{T}\end{bmatrix} = \begin{bmatrix}h_{11} & \ldots & h_{1N_{T}} \\\vdots & \ddots & \vdots \\h_{N_{R}1} & \ldots & h_{N_{R}N_{T}}\end{bmatrix}}} & \left\lbrack {{Equation}\mspace{14mu} 19} \right\rbrack\end{matrix}$

Meanwhile, in an actual channel, additive white Gaussian noise (AWGN) isadded through the channel matrix H. Accordingly, white noises n₁, n₂, .. . , n_(NR) added to the respective N_(R) Rx antennas are expressed asfollows in a vector form.

n=[n ₁ ,n ₂ , . . . ,n _(N) _(R) ]^(T)  [Equation 20]

The transmission signal, received signal, channel, and white noise mayhave the following relations in a multi-input multi-output antennacommunication system through modeling.

$\begin{matrix}{y = {\quad {\begin{bmatrix}y_{1} \\\vdots \\y_{N_{R}}\end{bmatrix} = {{{\begin{bmatrix}h_{11} & \ldots & h_{1N_{T}} \\\vdots & \ddots & \vdots \\h_{N_{R}1} & \ldots & h_{N_{R}N_{T}}\end{bmatrix}\begin{bmatrix}x_{1} \\\vdots \\x_{N_{T}}\end{bmatrix}} + \begin{bmatrix}n_{1} \\\vdots \\n_{N_{R}}\end{bmatrix}} = {{Hx} + n}}}}} & \left\lbrack {{Equation}\mspace{14mu} 21} \right\rbrack\end{matrix}$

Meanwhile, the number of rows and number of columns of a channel matrixH indicative of the state of a channel are determined by the number ofTx/Rx antennas. As described above, in the channel matrix H, the numberof rows becomes equal to the number of Rx antennas N_(R), and the numberof columns becomes equal to the number of Tx antennas N_(T). That is,the channel matrix H becomes an N_(R)×N_(T) matrix.

In general, the rank of a matrix is defined as a minimum number fromamong the number of rows and the number of columns that are independent.Accordingly, the rank of a matrix cannot be greater than the number ofrows or columns. For example, mathematically, the rank H of the channelmatrix H is limited as follows.

rank(H)≤min(N _(T) ,N _(R))  [Equation 22]

Furthermore, when eigen value decomposition is performed on the matrix,the rank may be defined as the number of eigen values other than 0 fromamong eigen values. As a similar method, when singular valuedecomposition (SVD) is performed on the rank, the rank may be defined asthe number of singular values other than 0. Accordingly, in the channelmatrix, a physical meaning of the rank may be said to be a maximumnumber capable of transmitting different information in a given channel.

In this specification, a “rank” for MIMO transmission indicates thenumber of paths capable of independently transmitting signals inspecific timing and a specific frequency resource, and “the number oflayers” indicates the number of signal streams transmitted through eachpath. In general, a transmission stage transmits layers having a numbercorresponding to the number of ranks used for signal transmission, andthus one rank has the same meaning as a layer number unless specificallydescribed.

As described above, an NB-IoT system refers to a system for supportingcommunication between terminals having the characteristics of a low costand low complexity, which uses a narrowband.

Furthermore, the NB-IoT system takes into consideration a connectionsituation between multiple terminals using a limited communicationresource and aims to support wider coverage than legacy LTE.

In order to obtain an effect of coverage extension through a limitednumber of resources (e.g., subcarriers), an NB-IoT system takes intoconsideration an uplink transmission method and repetition method usinga single tone or single subcarrier.

If single subcarrier (or tone) transmission is used, a wirelesscommunication system can solve problems, such as the shortage ofsubcarrier resources, extreme coverage support, etc. in terms of variousaspects.

Furthermore, single tone transmission supports π/2-BPSK modulation andπ/4-QPSK modulation.

Hereinafter, a method of defining (or configuring or designing) a PUSCHframe structure of NB-IoT proposed in this specification is described.

Specifically, this specification provides (1) a method of determiningthe position of a demodulation (DM)-reference signal (RS) symbol inorder to support a narrowband (NB)-PUSCH, (2) a method of generating aDM-RS sequence and mapping it to a symbol by taking into consideration aphase rotation, and (3) a method of configuring an initial phase (of adata symbol or DM-RS symbol for an NB-PUSCH).

Contents and methods proposed in this specification are limited to aPUSCH of NB-IoT and described, for convenience of description, but thecontents and methods may also be applied to uplink/downlink data channeland uplink/downlink control channel transmission in all of communicationsystems using single tone transmission.

In contents described hereunder, single tone transmission of NB-IoT isdescribed as an example, but is not limited thereto and may be appliedto multiple tone transmission of NB-IoT.

In this case, multiple tone (or subcarrier) transmission of NB-IoT mayuse 2, 3, 6 or 12 tones, for example.

Furthermore, a wireless device, a transmitter, a receiver and atransceiver used in this specification means a device capable oftransmitting at least one of the transmission of a signal and thereception of a signal, and may include a terminal, a base station, etc.

Furthermore, the wireless device supports an NB-IoT system and can alsosupport the legacy LTE system additionally.

Furthermore, hereinafter, embodiments have been classified forconvenience of description, and the embodiments may be combined andimplemented or may be independently performed.

First Embodiment: DM-RS Structure for NB-PUSCH Support of NB-IoT

The first embodiment provides contents for a DM-RS structure forsupporting an NB-PUSCH in an NB-IoT (or NB-LTE) system.

In this case, the DM-RS structure includes the position of a DM-RSsymbol in a slot, a subframe, a radio frame, a resource unit, etc.

Furthermore, in the NB-IoT system, a PUSCH may be used for thetransmission of control information in addition to data.

In NB-PUSCH transmission, channel estimation may be performed using aDM-RS for coherent demodulation.

In NB-IoT, a DM-RS needs to be designed by taking into considerationcoexistence with a legacy LTE system for supporting an inband scenario(or inband mode).

In particular, if an NB-IoT system operates in the inband mode, theposition of a DM-RS within a slot of NB-IoT needs to be designed toavoid a collision with a sounding reference signal (SRS) location oflegacy LTE.

Furthermore, a subframe structure of NB-IoT may be the same as ordifferent depending on subcarrier spacing.

That is, a subframe structure of NB-IoT may use the same structureregardless of subcarrier spacing (defined in NB-IoT) or may use adifferent subframe structure depending on subcarrier spacing.

If the same subframe structure is used regardless of subcarrier spacing,a terminal (e.g., UE) determines the structure of a subframe related toNB-PUSCH transmission through signaling for determining a subframeformat (to be described later).

In contrast, if a different subframe structure is used depending onsubcarrier spacing, a terminal may determine the structure of a subframein order to combine and use signaling information for determining asubframe format and signaling information for determining subcarrierspacing.

In NB-IoT, one DM-RS density may be fixed or one of several DM-RSdensities may be selected and used.

In this case, the DM-RS density is related to the number of DM-RSsymbols in which a DM-RS is transmitted, and may be expressed to have alarge or small number of DM-RS symbols.

If several DM-RS densities are supported, each terminal may receive apredefined subframe format through a control signal from a base station(e.g., eNodeB), may select one of the received subframe formats, and mayoperate.

Hereinafter, various subframe formats for a DM-RS are described indetail.

(1) Format 0 (Short DM-RS Sequence)

Format 0 shows a format using a short DM-RS sequence.

Format 0 may be divided into (1-1) and (1-2) based on spacing in which aDM-RS symbol is allocated. (1-1) and (1-2) may be divided into (1-1a)and (1-1b), and (1-2a) and (1-2b), respectively, depending on thelocation where a DM-RS symbol within a slot starts.

(1-1) 7 Symbol Spaced DM-RS Symbol Allocation

This method is a method of deploying or allocating DM-RS symbols in a7-symbol unit as in the existing legacy LTE system.

However, in NB-IoT, subcarrier spacing is 3.75 kHz. If DM-RS symbols areallocated to 4^(th) (I=3) and 11^(th) (I=10) symbols as in the legacyLTE system, the section in which the position of a DM-RS symbol overlapsthe position of an SRS symbol used in the legacy LTE system may occur.

I indicates a symbol index.

An SRS symbol is located in the last symbol, that is, a 14-th symbol(I=13) of each SF.

Accordingly, in an NB-PUSCH, a method of deploying a DM-RS symbol toanother symbol position in order to take into consideration coexistencewith the legacy LTE system needs to be taken into consideration.

FIG. 34 shows an example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

That is, FIG. 34 shows a diagram corresponding to the aforementioned(1-1a) and (1-1b).

As in (1-1a) of FIG. 34, a DM-RS may be mapped to the 1^(st) and 8^(th)symbols of one NB-subframe.

Alternatively, as in (1-1b) of FIG. 34, if a DM-RS symbol is mapped tothe 2^(nd) and 9^(th) symbols of one NB-subframe, a collision with alegacy SRS symbol can be prevented.

In this case, one NB-subframe may include two NB-slots, and each of theNB-slots may include 7 symbols.

The NB-subframe may be expressed as a time unit, time resource, etc.including a plurality of symbols.

(1-2) 6 (or 8) Symbol Spaced DM-RS Symbol Allocation

The (1-2) method is a method of unifying symbol indices within asubframe of a DM-RS symbol as an even number or odd number in order tosupport a case where a phase rotation is incorporated into a DM-RSsymbol.

In this case, the phase rotation may support π/2-BPSK and π/4-QPSK.

In single tone transmission of an NB-IoT system, π/2-BPSK and π/4-QPSKare supported in order to reduce a peak-to-average power ratio(PAPR)/cubic metric (CM). Accordingly, the structure of DM-RS symbolscan be supported by taking into consideration a phase rotation.

In NB-IoT, in order to support π/2-BPSK and π/4-QPSK, a constellationmust be rotated π/2 or π/4 every symbol. Accordingly, a constellationpoint used in each symbol is classified depending on whether a symbolindex is even or odd.

In order to design (or configure) systems using differentconstellations, a DM-RS sequence needs to be designed by taking intoconsideration a modulation method and a correlation characteristic thatis different depending on whether a (phase) rotation is applied.

If the constellation points of all of DM-RS symbols can be identicallyaligned, however, a DM-RS sequence can be easily designed because theconstellation points can use the existing sequence characteristic.

To this end, a method of aligning the index numbers of DM-RS symbols asan even or odd number is described with reference to (1-2) of FIG. 34.

As shown in FIG. 34, if the index numbers of two symbols are differently“6” and “8” within one subframe, the constellation points of all ofDM-RS symbols may be identically aligned.

Each of (1-2a) and (1-2b) of FIG. 34 shows an example of such a DM-RSsymbol allocation method.

(1-2a) of FIG. 34 shows that (spaced) DM-RS symbols are deployed in 8symbol spacing by allocating the DM-RS symbols to 1^(st) and 9^(th)symbol positions.

(1-2b) of FIG. 34 shows that DM-RS symbols are deployed in 6 symbolspacing by allocating the DM-RS symbol in 2^(nd) and 8^(th) symbolpositions.

(2) Format 1-A (x2 DM-RS Density)

Format 1-A shows an example in which DM-RS density has been doubledcompared to Format 0.

That is, Format 1-A shows a DM-RS symbol deployment structure if thenumber of DM-RS symbols has been doubled compared to Format 0.

If DM-RS density needs to be increased for channel estimation accuracy,the number of DM-RSs necessary for one subframe may increase.

In order to support such a case, a subframe of an NB-PUSCH in which anextended DM-RS sequence has been incorporated needs to be designed.

Accordingly, Format 1 (1-A, 1-B, 1-C) to be described below uses amethod of adding additional DM-RS symbols, generated due to an increaseof DM-RS density, to the front or rear of a DM-RS symbol position ofFormat 0.

Format 1-A supports a subframe structure if DM-RS density used in Format0 is doubled.

FIG. 35 shows another example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

That is, FIG. 35 shows the positions of DM-RS symbols to the front orrear of which DM-RS symbols have been added in the case of FIG. 34.

Each of (1-1a) and (1-1b) of FIG. 35 shows an example in which one DM-RSsymbol has been added at the back of each symbol in each of (1-1 a) and(1-1b) of FIG. 34. Each of (1-2a) and (1-2b) of FIG. 35 shows an examplein which one DM-RS symbol has been added at the front of each symbol ineach of (1-2a) and (1-2b) of FIG. 34.

(3) Format 1-B (x3 DM-RS Density)

Format 1-B shows an example in which DM-RS density has been tripledcompared to Format 0.

That is, Format 1-B shows a DM-RS symbol deployment structure if thenumber of DM-RS symbols is increased three times compared to Format 0.

FIG. 36 shows yet another example of a DM-RS symbol mapping method inNB-IoT proposed in this specification.

As shown in FIG. 36, in a system in which (1-1) of Format 0 is used,3^(rd) and 10^(th) symbols, and 5^(th) and 12^(th) symbols may beadditionally used for a DM-RS.

As described above, in Format 1-B, the position of a symbol that may beused is limited to avoid a collision with a legacy SRS.

That is, in Format 1-B, the 1^(st)˜3^(rd) symbols 3610 and8^(th)˜10^(th) symbols 3620 of a subframe may be used as DM-RS symbolsas in FIG. 36.

In this case, one NB-subframe includes two slots, and each slot may have7 symbols.

Accordingly, DMRS symbols in Format 1-B are positioned in 3 symbols inthe first of each slot, and the 3 symbols in the first indicate thefirst symbol, second symbol and third symbol of a slot.

In DM-RS symbol positions, such as Format 1-B, if orthogonal cover code(OCC) is taken into consideration, the OCC needs to be designed bytaking into consideration the influence of a phase rotation.

Single tone transmission of NB-IoT uses a phase rotation scheme in whicha reference constellation point varies in each symbol in order toimprove the PAPR and CM performance.

In this case, although contiguous two symbols indicate the same value,different values may be expressed due to the influence of a phaserotation. If the existing method of expressing OCC is applied withoutany change, the characteristics of OCC may not be maintained.

For example, if an orthogonal sequence used in the normal CP conditionsof the (legacy LTE) PUCCH formats 1, 1a is reused without any change,the characteristics of OCC may be broken due to the influence of thephase rotation of a second DM-RS symbol.

Table 8 is a table showing an example of orthogonal sequences applied tothe legacy LTE PUCCH formats 1, 1a and 1b.

TABLE 8 Sequence index  

  (n_(s)) Normal cyclic prefix Extended cyclic prefix 0 [1 1 1] [1 1] 1[1 e^(j2π/3) e^(j4π/3)] [1 −1] 2 [1 e^(j4π/3) e^(j2π/3)] N/A

In order to prevent the characteristics of OCC from being broken due toa phase rotation, single tone transmission of NB-IoT needs to bedesigned by taking into consideration the influence of a phase rotationin the design of OCC.

As described in FIG. 36, in the case of the contiguous 3 symbols, thefirst and the third symbols use the same phase rotation, but the secondsymbol has a different phase rotation value.

For example, if pi/2 BPSK modulation is used, the second symbol has aphase difference of pi/2.

In this case, pi indicates π.

In order to maintain the orthogonal property by taking intoconsideration a rotated phase value, new OCC may be designed in a formin which an effect of a phase rotation has been compensated for in theOCC design of the existing legacy LTE.

In this case, OCC sequences of the existing legacy LTE may be used inDM-RS symbols of NB-IoT.

OCC for the position of a DM-RS symbol of a Format 1-B form u singPi/2-BPSK may have a form, such as Table 10.

TABLE 10 Sequence index Orthogonal sequence 0 [1 1 1] 1 [1 e^(jπ/6)e^(j4π/3)] 2 [1 e^(j5π/6) e^(j2π/3)]

(4) Format 1-C(x3 DM-RS Density)

Format 1-C shows yet another example in which DM-RS density has beentripled compared to Format 0.

That is, like Format 1-B, Format 1-C shows a DM-RS symbol deploymentstructure if the number of DM-RS symbols has been increased three timescompared to Format 0.

FIG. 37 shows another example of a DM-RS symbol mapping method in NB-IoTproposed in this specification.

In FIG. 37, in a system using (1-1) of Format 0, three DM-RS symbols areused and a case where OCC is applied is taken into consideration.

If three DM-RS symbols are present within one NB-slot and OCC is appliedto distinguish between the three DM-RS symbols, the orthogonal propertymay not be maintained in terms of the characteristic of single tonetransmission to which a phase rotation is applied.

For example, if three DM-RS symbols are contiguously deployed as inFormat 1-B, different phase rotations are applied between the contiguoussymbols and thus the characteristics of OCC is broken.

In order to prevent such a situation, symbol positions may be determinedso that the same phase rotation is applied to three DM-RS symbols withinone slot.

Furthermore, the positions may be determined by avoiding a positionwhere an SRS may occur.

If M-PSK modulation is used, when a phase rotation rule applied to ann-th symbol is exp(j*pi/M*(n mod 2)), the same phase rotation value ismultiplied between even index symbols or odd index symbols.

In this case, pi means π, and an M value is a modulation order value andmay be 2, 4, etc.

The locations of DM-RS symbols may be restricted to use only an evenindex or odd index using such a characteristic. The location of a DM-RSsymbol defined by such a characteristic may not overlap the position ofa (legacy LTE) SRS symbol.

As an example in which such a condition is taken into consideration, thepositions of DM-RS symbols, such as FIG. 37, may be taken intoconsideration.

The positions of DM-RS symbols shown in FIG. 37 are 1^(st), 3^(rd), and5^(th) symbols in each slot. All the corresponding symbols aremultiplied by a phase rotation value of the same degree and does notoverlap the position of a legacy LTE SRS symbol.

If OCC is applied to the aforementioned positions where multiple DM-RSsymbols are determined, a method of taking into consideration theinfluence of a phase rotation may also be applied to 15 kHz subcarrierspacing in the same manner.

FIG. 38 shows yet another example of a DM-RS symbol mapping method inNB-IoT proposed in this specification.

That is, FIG. 38 shows an example of the locations of three DM-RSsymbols in 15 kHz subcarrier spacing.

From FIG. 38, it may be seen that 2^(nd), 4^(th), and 6^(th) symbolswithin one slot are used as DM-RS symbols.

Second Embodiment: Method of Generating DM-RS Sequence in NB-IoT

The second embodiment provides a method of generating a DM-RS sequencefor an NB-PUSCH in an NB-IoT system.

Uplink transmission of NB-IoT supports two modulation methods, that is,π/2-BPSK and π/4-QPSK, in order to support single tone transmission.

Accordingly, uplink transmission of NB-IoT requires the design of aDM-RS sequence for supporting two different transmission modes (singletone transmission of a π/2-BPSK modulation method and single tonetransmission of a π/4-QPSK modulation method).

In this case, in the case of single tone transmission of NB-IoT, thesize of a base resource unit (RU) includes a total of 8 subframes.

In NB-IoT, one subframe includes 2 slots, and the base RU may include 16slots.

If a DM-RS sequence is mapped in the time axis, the length of anavailable DM-RS sequence is restricted to 16.

Accordingly, a ZC-sequence may not be useful for use of a DM-RSsequence.

Furthermore, since NB-IoT is sensitive to PAPR/CM performance, there isa need for the structure or design of a sequence capable of guaranteeinga low PAPR/CM value in NB-IoT.

As described above, uplink single tone transmission of NB-IoT uses theπ/2-BPSK and π/4-QPSK modulation methods in order to guarantee a lowPAPR/CM.

However, the subframe structure of an NB-PUSCH has a structure in whicha DM-RS symbol is located between the positions of symbols for data.

Accordingly, the subframe structure of an NB-PUSCH needs to be designedby taking into consideration the phase rotation of a DM-RS symbol.

To this end, in this specification, when a DM-RS sequence of an NB-PUSCHis generated, a DM-RS sequence based on π/2-BPSK and π/4-QPSK isgenerated.

In this case, a modulation method of a DM-RS symbol may be the same as amodulation method of a data symbol or may be different from a modulationmethod of a data symbol according to circumstances.

In NB-IoT, a method of applying a phase rotation to a DM-RS symbol maybe divided into (1) a method (first method) of generating the finalsequence by generating a base sequence based on common BPSK or QPSK andthen applying a phase rotation and (2) a method (second method) ofgenerating a sequence into which a phase rotation has been incorporatedby taking into consideration the position of a DM-RS symbol.

The first method has an advantage in that it can be used using theexisting method of generating a sequence regardless of the position of aDM-RS symbol, but needs to take into consideration that thecharacteristic of a sequence, such as a correlation characteristic aftera phase rotation is generated, must be maintained.

The second method requires the design of a new sequence in which acorrelation characteristic between sequences is taken into considerationif symbol indices within a subframe are not unified as an even number orodd number.

The second method has an advantage in that it can use the existingsequence if symbol indices within a subframe are fixed to an even or oddnumber.

The first method and second method of applying a phase rotation to aDM-RS symbol are different in a method of generating a DM-RS sequence,but may be the same in the form of a resulting DM-RS sequence.

Hereinafter, a sequence generation method is described based on thefirst method. In this case, the results of the first method may also bedirectly applied to a sequence of the second method.

If symbol indices of a DM-RS within a subframe sequentially occur ineven and odd numbers, two DM-RS sequences may be allocated to evennumber DM-RS symbols and odd number DM-RS symbols, respectively.

The corresponding method has advantages in that the correlation propertybetween DM-RS symbols can be maintained and DM-RS symbol allocation of 7symbol spacing can also be used.

In this specification, the case of an NB-IoT PUSCH using (or supporting)single-tone transmission is described as an example, but the methodsproposed in this specification may also be applied to an NB-IoT systemusing multi-tone (or multi-subcarrier) transmission or othercommunication systems.

Hereinafter, a phase rotation method for a data symbol and DM-RS symbolthrough various methods (method 1 to method 4) is described in detail.

Uplink single tone transmission of NB-IoT uses the π/2-BPSK and π/4-QPSKmodulation methods.

As described above, in the subframe structure of an NB-PUSCH, a DM-RSsymbol is located between the positions of symbols for data.Accordingly, the subframe structure of an NB-PUSCH needs to be designedby taking into consideration a phase rotation of a DM-RS symbol.

Accordingly, a phase rotation method for a data symbol and DM-RS symbol,proposed in this specification, may take into consideration thefollowing four methods.

Phase rotation information of a DM-RS symbol may be considered to beinformation known to both transmission and reception devices evenwithout the transmission and reception of additional control informationbecause it is determined by an agreed symbol position.

Accordingly, information of a DM-RS symbol attributable to a phaserotation is not damaged.

A combination of a data symbol modulation method and a DM-RS symbolmodulation method may select at least one of the following four methodsfor each data symbol modulation method and operate.

(Method 1) π/2-BPSK Data and π/2-BPSK DM-RS Sequence

First, the method 1 is described.

The method 1 is a method of applying π/2-BPSK to both a data symbol anda DM-RS symbol.

That is, in the method 1, if π/2-BPSK modulation is used for datatransmission and a π/2-BPSK DM-RS sequence is used for DM-RStransmission, a change in the constellation point of each symbol has adifference of π/2 for each symbol regardless of a data symbol and aDM-RS symbol

If a data symbol and a DM-RS symbol use the same BPSK-series in a phaserotation as in the method 1, a PAPR/CM reduction can be minimized.

A method of generating a DM-RS sequence according to the method 1 may beexpressed like Equation 23.

$\begin{matrix}{{{r_{u,i}\left( {n,m} \right)} = e^{j{({\frac{{\phi {(n)}}\pi}{2} + \frac{{\gamma {(m)}}\pi}{2} + {\varnothing {(i)}}})}}},{0 \leq n \leq {M^{RU} - 1}},{1 \leq m \leq 14}} & \left\lbrack {{Equation}\mspace{14mu} 23} \right\rbrack\end{matrix}$

In this case, n indicates an index according to the sequence of DM-RSsymbols within a sequence. An M^(RU) value is a value to determine thelength of the sequence and indicates the number of DM-RS symbolsallocated to one subcarrier within a resource unit.

φ(n) is a value previously agreed to define the sequence and maygenerate multiple sequences by defining different φ(n) values dependingon a u value.

In this case, the u value may indicate a sequence group number. Forexample, the u value may have a value of 0 to 29 (u∈{0, 1, . . . , 29}).

Furthermore, φ(n) may use a computer generate random binary number andmay be defined through sequences of series that satisfy the correlationproperty such as a PN sequence, orthogonal sequence series such as aWalsh sequence, etc. Table 11 shows an example of a method of definingφ(n).

TABLE 11 u φ(0), . . . , φ(15) 0 0 1 1 0 1 1 1 0 1 1 1 0 1 1 0 1

Furthermore, as another method of generating φ(n), a method of randomlygenerating a DM-RS symbol in a symbol unit without generating apredefined base sequence may be taken into consideration.

Such a method of generating a DM-RS symbol may be defined as a functionof a cell ID and the index number of a time unit, such as a resourceunit index, frame index, subframe index, slot index or symbol index.

The generation of a DM-RS and channel estimation is always possiblebecause a function and necessary variables for generating the randomgeneration DM-RS symbol are information known to both an eNodeB and UEs.

Furthermore, if such a method of generating a DM-RS symbol (method ofrandomly generating a DM-RS symbol in a symbol unit) is used, thegeneration of a DM-RS symbol suitable for various conditions is possiblebecause the length of a sequence has not been determined.

Furthermore, m means an index number indicated by a symbol within onesubframe or within a time unit in which a phase rotation is performed.

γ(m) is a value for expressing a phase rotation attributable to a symbolindex within a subframe and may have a value of 1 or 0 depending onwhether the index of a symbol is even or odd.

A formula expression of γ(m) may be defined like Equation 24.

γ(m)=1−mod(m,2)  [Equation 24]

Alternatively, γ(m) may be a value to express the index of a symbolwithin a subframe index.

In this case, the m value starts at the point at which a subframe startsand rises up to the point at which the corresponding subframe ends.

Furthermore, a new m value starts at a subframe boundary point at whicha corresponding subframe ends and a new subframe starts.

For example, if 14 OFDM symbols are present within one subframe, γ(m)may be expressed using Equation 25.

γ(m)=m, m=1, . . . ,14  [Equation 25]

Alternatively, γ(m) may be a function having a combination of a subframe(or slot) index and a symbol index.

In this case, the m value may be determined to be a value including acombination of a subframe (or slot) index and a symbol index.

If the value of the subframe index is defined to be p and the value ofthe symbol index is defined to be q, the value of γ(m) may be expressedas a function of p and q.

For example, if N_(SF) OFDM symbols are present within one subframe,γ(m) may be expressed using Equation 26.

γ(m)=m=N _(SF)(p−1)+q, p=1,2, . . . q=1, . . . ,N _(SF)  [Equation 26]

In this case, if the m value is expressed as a combination of a slotindex and a symbol index, when N_(Slot) OFDM symbols are present in oneslot, γ(m) may be expressed using Equation 27.

γ(m)=m=N _(Slot)(p−1)+q, p=1,2, . . . q=1, . . . ,7  [Equation 27]

In such setting of γ(m), if the transmission of a terminal (e.g., UE) isnot continuous, a rule to determine γ(m) before or after discontiguoustransmission may be determined.

Such a situation may be applied to all of common cases where a terminaltemporarily stops transmission and performs retransmission (ortransmission again) after a specific time unit.

For example, the discontiguous transmission situation may include acontinuity restriction to an UL resource according to a TDD structure,subframe allocation for a PRACH, the position of an unavailable subframeset by a system, and the restriction of contiguous transmissionattributable to a measurement gap, etc.

As one method for determining a method of calculating γ(m) in thediscontiguous transmission, a method of newly starting the calculationof γ(m) at the point at which the transmission of a terminal startsagain after it stops may be taken into consideration.

Alternatively, another method may include a method of performing thecalculation by taking into consideration a time unit in which γ(m) hasbeen accumulated at the point at which transmission starts again whilecontinuing to take into consideration the interval of a time unit, suchas a subframe number or symbol number, even in the section in whichtransmission has stopped.

In this case, a subframe index or symbol index may be determined by asystem frame number (SFN).

ø(i) is a value to set an initial phase and indicates a value todetermine the phase rotation value of the first symbol of a unit inwhich a phase rotation is performed.

(Method 2) π/2-BPSK Data and π/4-QPSK DMRS Sequence

The method 2 is described below.

The method 2 is a method of applying π/2-BPSK to a data symbol andπ/4-QPSK to a DM-RS symbol.

In the method 2, that is, in the method of using π/2-BPSK datamodulation and π/4-QPSK DM-RS modulation, two methods (first method andsecond method) may be basically taken into consideration.

(1) The first method is a method of maintaining a symbol withoutperforming a phase rotation on a DM-RS symbol if π/2-BPSK modulation isused for data transmission and a π/4-QPSK DM-RS sequence is used forDM-RS transmission.

This is for reducing a PAPR/CM value by preventing the occurrence ofzero crossing.

A method of generating a DM-RS sequence according to the first method ofthe method 2 may be expressed like Equation 28.

$\begin{matrix}{{{r_{u,i}(n)} = e^{j{({\frac{{\phi {(n)}}\pi}{4} + {\varnothing {(i)}}})}}},{0 \leq n \leq {M^{RU} - 1}}} & \left\lbrack {{Equation}\mspace{14mu} 28} \right\rbrack\end{matrix}$

In this case, n indicates an index according to the sequence of DM-RSsymbols within a sequence, and an M^(RU) value is a value to determinethe length of the sequence and indicates the number of DM-RS symbolsallocated to one subcarrier within a resource unit.

φ(n) is a value previously agreed to define the sequence and maygenerate multiple sequences by defining different φ(n) values dependingon a u value.

In this case, the u value may indicate a sequence group number. Forexample, the u value may have a value of 0 to 29 (u∈{0, 1, . . . , 29}).

Furthermore, φ(n) may use a computer generate random binary number, andmay be defined through sequences of series that satisfy the correlationproperty such as a PN sequence, orthogonal sequence series such as aWalsh sequence, etc. Table 12 shows an example of a method of definingφ(n).

TABLE 12 u φ(0), . . . , φ(15) 0 −1 3 1 3 3 −3 −1 1 −3 3 3 −1 3 1 −1 −3

Furthermore, as another method of generating φ(n), a method of randomlygenerating a DM-RS symbol in a symbol unit without using a predefinedbase sequence may be taken into consideration.

Such a method of generating a DM-RS symbol may be defined as a functionof a cell ID and the index number of a time unit, such as a resourceunit index, frame index, subframe index, slot index or symbol index.

The generation of a DM-RS and channel estimation is always possiblebecause a function and necessary variables for generating the randomgeneration DM-RS symbol are information known to both an eNodeB and UEs.

Furthermore, if such a method of generating a DM-RS symbol (method ofrandomly generating a DM-RS symbol in a symbol unit) is used, thegeneration of a DM-RS symbol suitable for various conditions is possiblebecause the length of a sequence has not been determined.

(2) The second method is a method of selecting sequences in which a basesequence satisfies BPSK characteristics from among DM-RS sequencesgenerated through π/4-QPSK modulation and using the selected sequencesas π/2-BPSK DM-RS sequence.

The second method has an advantage in that a phase rotation operationcan be continuously performed identically from the viewpoint of aterminal while unifying DM-RS base sequence generation methods into oneregardless of a data symbol modulation method.

A method of generating a DM-RS sequence according to the second methodof the method 2 may be expressed like Equation 29.

$\begin{matrix}{{{r_{u,i}\left( {n,m} \right)} = e^{j{({\frac{{\phi {(n)}}\pi}{4} + \frac{\pi}{4} + \frac{{\gamma {(m)}}\pi}{2} + {\varnothing {(i)}}})}}},{0 \leq n \leq {M^{RU} - 1}},{1 \leq m \leq 14}} & \left\lbrack {{Equation}\mspace{14mu} 29} \right\rbrack\end{matrix}$

In this case, n indicates an index according to the sequence of DM RSsymbols within a sequence. An M^(RU) value is a value to determine thelength of the sequence and indicates the number of DM-RS symbolsallocated to one subcarrier within a resource unit.

φ(n) is a value previously agreed to define the sequence and maygenerate multiple sequences by defining different φ(n) values dependingon a u value.

In this case, the u value may indicate a sequence group number. Forexample, the u value may have a value of 0 to 29 (u∈{0, 1, . . . , 29}).

Furthermore, φ(n) may use a computer generate random binary number, andmay be defined through sequences of series that satisfy the correlationproperty such as a PN sequence, orthogonal sequence series such as aWalsh sequence, a sequence using a modified form of a DFT matrix, etc.

Instead, in order to satisfy continuity with π/2-BPSK modulation, only agroup including only 1 and −3 or −1 and 3 is selected and used as thevalue of φ(n).

$A + \frac{\pi}{4}$

value is a value for aligning a constellation point with a π/2-BPSK datasymbol and may be excluded.

Table 13 shows an example of a method of defining φ(n).

TABLE 13 u φ(0), . . . , φ(15) 0 −1 3 −1 3 3 3 −1 −1 3 3 3 −1 3 3 −1 3 11 −3 1 1 −3 −3 −3 1 1 −3 1 −3 −3 1 1 −3

Furthermore, as another method of generating φ(n), a method of randomlygenerating a DM-RS symbol in a symbol unit without using a predefinedbase sequence may be taken into consideration.

Such a method of generating a DM-RS symbol may be defined as a functionof a cell ID and the index number of a time unit, such as a resourceunit index, frame index, subframe index, slot index or symbol index.

The generation of a DM-RS and channel estimation is always possiblebecause a function and necessary variables for generating the randomgeneration DM-RS symbol are information known to both an eNodeB and UEs.

Furthermore, if such a method of generating a DM-RS symbol (method ofrandomly generating a DM-RS symbol in a symbol unit) is used, thegeneration of a DM-RS symbol suitable for various conditions is possiblebecause the length of a sequence has not been determined.

Furthermore, m means an index number indicated by a symbol within onesubframe or within a time unit in which a phase rotation is performed.

γ(m) is a value for expressing a phase rotation attributable to a symbolindex within a subframe, and may have a value of 1 or 0 depending onwhether the index of a symbol is even or odd.

A formula expression of γ(m) may be defined like Equation 30.

γ(m)=1−mod(m,2)  [Equation 30]

Alternatively, γ(m) may have one of values of 0, 1, 2, and 3 dependingon a method of designing a system performing a phase rotation.

In this case, the formula expression of γ(m) may be defined likeEquation 31.

In this case, in the method of a phase rotation, a DM-RS phase rotationmethod with a UE using a π/4-QPSK data symbol and a π/4-QPSK DM-RSsymbol may be made identical although it is different from a data symbolpart.

γ(m)=[4−mod(m,4)]/2  [Equation 31]

Alternatively, γ(m) is a value to express the index of a symbol within asubframe index.

In this case, the m value starts at the point at which a subframe startsand rises up to the point at which the corresponding subframe ends.

Furthermore, a new m value starts at a subframe boundary point at whicha corresponding subframe ends and a new subframe starts.

For example, if 14 OFDM symbols are present within one subframe, γ(m)may be expressed using Equation 32.

γ(m)=m, m=1, . . . ,14  [Equation 32]

Alternatively, γ(m) may be a function including a combination of asubframe (or slot) index and a symbol index.

In this case, the m value may be determined to be a value including acombination of a subframe (or slot) index and a symbol index.

If the value of the subframe index is defined to be p and the value ofthe symbol index is defined to be q, the value of γ(m) may be expressedas a function of p and q.

For example, if N_(SF) OFDM symbols are present within one subframe,γ(m) may be expressed using Equation 33.

γ(m)=m=N _(SF)(p−1)+q, p=1,2, . . . q=1, . . . ,N _(SF)  [Equation 33]

In this case, if the m value is expressed as a combination of a slotindex and a symbol index, when N_(slot) OFDM symbols are present withinone slot, γ(m) may be expressed using Equation 34.

γ(m)=m=N _(Slot)(p−1)+q, p=1,2, . . . q=1, . . . ,7  [Equation 34]

In such setting of γ(m), if the transmission of a terminal (e.g., UE) isnot contiguous, a rule to determine γ(m) before or after discontiguoustransmission may be determined.

Such a situation may be applied to all of common cases in which aterminal temporarily stops transmission and performs retransmission (ortransmission again) after a specific time unit.

For example, the situation of the discontiguous transmission may includea continuity restriction to an UL resource according to a TDD structure,subframe allocation for a PRACH, the position of an unavailable subframeset by a system, and the restriction of contiguous transmissionattributable to a measurement gap, etc.

As one method for determining a method of calculating γ(m) in thediscontiguous transmission, a method of newly starting the calculationof γ(m) at the point at which the transmission of a terminal startsagain after it is stopped may be taken into consideration.

Alternatively, another method may include a method of performing thecalculation by taking into consideration a time unit in which γ(m) hasbeen accumulated at the point at which transmission starts again whilecontinuing to take into consideration the interval of a time unit, suchas a subframe number or symbol number, even in the section in whichtransmission has stopped.

In this case, a subframe index or symbol index may be determined by asystem frame number (SFN).

ø(i) is a value to set an initial phase and indicates a value todetermine the phase rotation value of the first symbol of a unit inwhich a phase rotation is performed.

(Method 3) π/4-QPSK Data and π/2-BPSK DMRS Sequence

The method 3 is described below.

The method 3 is a method of applying π/4-QPSK to a data symbol andπ/2-BPSK to a DM-RS symbol.

That is, in the method 3, if π/4-QPSK modulation is used for datatransmission and a π/2-BPSK DM-RS sequence is used for DM-RStransmission, a change in the constellation point of each symbol has adifference of π/4 in each symbol regardless of a data symbol and a DM-RSsymbol.

This is for reducing a PAPR/CM value by preventing the occurrence ofzero crossing.

According to the method 3, a method of generating a DM-RS sequence maybe expressed like Equation 35.

$\begin{matrix}{{{r_{u,i}\left( {n,m} \right)} = e^{j{({\frac{{\phi {(n)}}\pi}{2} + \frac{{\gamma {(m)}}\pi}{4} + {\varnothing {(i)}}})}}},{0 \leq n \leq {M^{RU} - 1}},{1 \leq m \leq 14}} & \left\lbrack {{Equation}\mspace{14mu} 35} \right\rbrack\end{matrix}$

In this case, n indicates an index according to the sequence of DM-RSsymbols within a sequence. An M^(RU) value is a value to determine thelength of the sequence and indicates the number of DM-RS symbolsallocated to one subcarrier within a resource unit.

φ(n) is a value previously agreed to define the sequence and maygenerate multiple sequences by defining different φ(n) values dependingon a u value.

In this case, the u value may indicate a sequence group number. Forexample, the u value may have a value of 0 to 29 (u∈{0, 1, . . . , 29}).

Furthermore, φ(n) may use a computer generate random binary number andmay be defined through sequences of series that satisfy the correlationproperty such as a PN sequence, orthogonal sequence series such as aWalsh sequence, etc.

Table 14 shows an example of a method of defining φ(n).

TABLE 14 u φ(0), . . . , φ(15) 0 0 1 1 0 1 1 1 0 1 1 1 0 1 1 0 1

Furthermore, as another method of generating φ(n), a method of randomlygenerating a DM-RS symbol in a symbol unit without using a predefinedbase sequence may be taken into consideration.

Such a method of generating a DM-RS symbol may be defined as a functionof a cell ID and the index number of a time unit, such as a resourceunit index, frame index, subframe index, slot index or symbol index.

The generation of a DM-RS and channel estimation is always possiblebecause a function and necessary variables for generating a randomgeneration DM-RS symbol are information known to both an eNodeB and UEs.

Furthermore, if such a method of generating a DM-RS symbol (method ofrandomly generating a DM-RS symbol in a symbol unit) is used, thegeneration of a DM-RS symbol suitable for various conditions is possiblebecause the length of the sequence has not been determined.

Furthermore, m means an index number indicated by a symbol within onesubframe or within a time unit in which a phase rotation is performed.

γ(m) is a value for expressing a phase rotation attributable to a symbolindex within a subframe, and may have a value of 1 or 0 depending onwhether the index of a symbol is even or odd.

A formula expression of γ(m) may be defined like Equation 36.

γ(m)=1−mod(m,2)  [Equation 36]

Alternatively, γ(m) may have one of values of 0, 1, 2, and 3 dependingon a method of designing a system that performs a phase rotation.

In this case, the formula expression of γ(m) may be defined likeEquation 37.

In this case, in the method of a phase rotation, a DM-RS phase rotationmethod with a UE using a π/4-QPSK data symbol and a π/4-QPSK DM-RSsymbol may be made identical although it is different from a data symbolpart.

γ(m)=[4−mod(m,4)]/2  [Equation 37]

Alternatively, γ(m) may be a value to express the index of a symbolwithin a subframe index.

In this case, the m value starts at the point at which a subframe startsand rises up to the point at which the corresponding subframe ends.

Furthermore, a new m value starts at a subframe boundary point at whicha corresponding subframe ends and a new subframe starts.

For example, if 14 OFDM symbols are present within one subframe, γ(m)may be expressed using Equation 38.

γ(m)=m, m=1, . . . ,14  [Equation 38]

Alternatively, γ(m) may be a function including a combination of asubframe (or slot) index and a symbol index.

In this case, the m value may be determined to be a value having acombination of a subframe (or slot) index and a symbol index.

If the value of the subframe index is defined to be p and the value ofthe symbol index is defined to be q, the value of γ(m) may be expressedas a function of p and q.

For example, if N_(SF) OFDM symbols are present within one subframe,γ(m) may be expressed using Equation 39.

γ(m)=m=N _(SF)(p−1)+q, p=1,2, . . . q=1, . . . ,N _(SF)  [Equation 39]

In this case, if the m value is expressed as a combination of a slotindex and a symbol index, when N_(Slot) OFDM symbols are present withinone slot, γ(m) may be expressed using Equation 40.

γ(m)=m=N _(Slot)(p−1)+q, p=1,2, . . . q=1, . . . ,7  [Equation 40]

In such setting of γ(m), if the transmission of a terminal (e.g., UE) isnot continuous, a rule to determine γ(m) before or after discontiguoustransmission may be determined.

Such a situation may be applied to all of common cases where a terminaltemporarily stops transmission and performs retransmission (ortransmission again) after a specific time unit.

For example, the situation of the discontiguous transmission may includea continuity restriction to an UL resource according to a TDD structure,subframe allocation for a PRACH, the position of an unavailable subframeset by a system, and the restriction of contiguous transmissionattributable to a measurement gap, etc.

As one method for determining a method of calculating γ(m) in thediscontiguous transmission, a method of newly starting the calculationof γ(m) at the point at which the transmission of a terminal startsagain after it stops may be taken into consideration.

Alternatively, another method may include a method of performing thecalculation by taking into consideration a time unit in which γ(m) hasbeen accumulated at the point at which transmission starts again whilecontinuing to take into consideration the interval of a time unit, suchas a subframe number or symbol number, even in the section in whichtransmission has stopped.

In this case, a subframe index or symbol index may be determined by asystem frame number (SFN).

ø(i) is a value to set an initial phase and indicates a value todetermine the phase rotation value of the first symbol of a unit inwhich a phase rotation is performed.

The method 3, that is, the method using π/4-QPSK data modulation andπ/2-BPSK DM-RS modulation, may be a method for unifying methods ofgenerating DM-RS sequences between terminals using different modulation.

Accordingly, the same sequence may be used with a different terminalusing π/2-BPSK data modulation within one cell. A different sequence foronly terminals using π/4-QPSK data modulation may be used.

(Method 4) π/4-QPSK Data and π/4-QPSK DMRS Sequence

The method 4 is described below.

The method 4 is a method of applying π/4-QPSK to both a data symbol anda DM-RS symbol.

That is, in the method 4, if π/4-QPSK modulation is used for datatransmission and a π/4-QPSK DM-RS sequence is used for DM-RStransmission, a change in the constellation point of each symbol has adifference of π/4 in each symbol regardless of a data symbol and a DM-RSsymbol.

The method 4 is for reducing a PAPR/CM value by preventing theoccurrence of zero crossing.

According to the method 4, a method of generating a DM-RS sequence maybe expressed like Equation 41.

$\begin{matrix}{{{r_{u,i}\left( {n,m} \right)} = e^{j{({\frac{{\phi {(n)}}\pi}{2} + \frac{{\gamma {(m)}}\pi}{2} + \mspace{11mu} {(i)}})}}},{0 \leq n \leq {M^{RU} - 1}},{1 \leq m \leq 14}} & \left\lbrack {{Equation}\mspace{14mu} 41} \right\rbrack\end{matrix}$

In this case, n indicates an index according to the sequence of DM-RSsymbols within a sequence. An M^(RU) value is a value to determine thelength of the sequence and indicates the number of DM-RS symbolsallocated to one subcarrier within a resource unit.

φ(n) is a value previously agreed to define the sequence.

Multiple sequences are generated according to the u value by defining adifferent (φ(n) value.

In this case, the u value may indicate a sequence group number. Forexample, the u value may have a value of 0 to 29 (u□{0, 1, . . . , 29}).

Furthermore, φ(n) may use a computer generate random binary number andmay be defined through sequences of series that satisfy the correlationproperty such as a PN sequence, orthogonal sequence series such as aWalsh sequence, etc. Table 15 shows an example of a method of definingφ(n).

TABLE 15 u φ(0), . . . , φ(15) 0 −1 3 1 3 3 −3 −1 1 −3 3 3 −1 3 1 −1 −3

Furthermore, as another method of generating φ(n), a method of randomlygenerating a DM-RS symbol in a symbol unit without using a predefinedbase sequence may be taken into consideration.

Such a method of generating a DM-RS symbol may be defined as a functionof a cell ID and the index number of a time unit, such as a resourceunit index, frame index, subframe index, slot index or symbol index.

The generation of a DM-RS and channel estimation is always possiblebecause a function and necessary variables for generating a randomgeneration DM-RS symbol are information known to both an eNodeB and UEs.

Furthermore, if such a method of generating a DM-RS symbol (method ofrandomly generating a DM-RS symbol in a symbol unit) is used, thegeneration of a DM-RS symbol suitable for various conditions is possiblebecause the length of the sequence has not been determined.

Furthermore, m means an index number indicated by a symbol within onesubframe or within a time unit in which a phase rotation is performed.

γ(m) is a value for expressing a phase rotation attributable to a symbolindex within a subframe, and may have a value of 1 or 0 depending onwhether the index of a symbol is even or odd.

A formula expression of γ(m) may be defined like Equation 42.

γ(m)=1−mod(m,2)  [Equation 42]

Alternatively, γ(m) may have one of values of 0, 1, 2, and 3 dependingon a method of designing a system that performs a phase rotation of adata symbol.

In this case, γ(m) may be defined like Equation 43.

γ(m)=4−mod(m,4)  [Equation 43]

Alternatively, γ(m) may be a value to express the index of a symbolwithin a subframe index.

In this case, the m value starts at the point at which a subframe startsand rises up to the point at which the corresponding subframe ends.

Furthermore, a new m value starts at a subframe boundary point at whicha corresponding subframe ends and a new subframe starts.

For example, if 14 OFDM symbols are present within one subframe, γ(m)may be expressed using Equation 44.

γ(m)=m, m=1, . . . ,14  [Equation 44]

Alternatively, γ(m) may be a function including a combination of asubframe (or slot) index and a symbol index.

In this case, the m value may be determined to be a value having acombination of a subframe (or slot) index and a symbol index.

If the value of a subframe index is defined to be p and the value of asymbol index is defined to be q, the value of γ(m) may be expressed as afunction of p and q.

For example, if N_(SF) OFDM symbols are present within one subframe,γ(m) may be expressed using Equation 45.

γ(m)=m=N _(SF)(p−1)+q, p=1,2, . . . q=1, . . . ,N _(SF)  [Equation 45]

In this case, if the m value is expressed as a combination of a slotindex and a symbol index, when N_(Slot) OFDM symbols are present withinone slot, γ(m) may be expressed using Equation 46.

γ(m)=m=N _(Slot)(p−1)+q, p=1,2, . . . q=1, . . . ,7  [Equation 46]

In such setting of γ(m), if the transmission of a terminal (e.g., UE) isnot contiguous, a rule to determine γ(m) before or after discontiguoustransmission may be determined.

Such a situation may be applied to all of common cases in which aterminal temporarily stops transmission and performs retransmission (ortransmission again) after a specific time unit.

For example, the situation of the discontiguous transmission may includea continuity restriction to an UL resource according to a TDD structure,subframe allocation for a PRACH, the position of an unavailable subframeset by a system, and the restriction of contiguous transmissionattributable to a measurement gap, etc.

As one method for determining a method of calculating γ(m) in thediscontiguous transmission, a method of newly starting the calculationof γ(m) at the point at which the transmission of a terminal startsagain after it is stopped may be taken into consideration.

Alternatively, another method may include a method of performing thecalculation by taking into consideration a time unit in which γ(m) hasbeen accumulated at the point at which transmission starts again whilecontinuing to take into consideration the interval of a time unit, suchas a subframe number or symbol number, even in the section in whichtransmission has stopped

In this case, a subframe index or symbol index may be determined by asystem frame number (SFN).

□(i) is a value to set an initial phase and indicates a value todetermine the phase rotation value of the first symbol of a unit inwhich a phase rotation is performed.

Third Embodiment: Phase Initialization Method

Next, the third embodiment provides a method of configuring an initialphase in order to support single tone transmission in NB-IoT uplinkusing π/2-BPSK and π/4-QPSK.

In this case, in order to use both π/2-BPSK modulation and π/4-QPSKmodulation, a wireless communication system needs to identically provideboth a transmitter and receiver with information regarding that thestart point of a phase rotation uses which phase.

This is contents corresponding to both a data symbol and a DM-RS symbol.

Accordingly, a base station needs to determine a method of determiningthat the symbol of timing when (data or DM-RS) transmission starts useswhich phase and a method regarding that an initial phase must beinitialized in which cycle and to share them with a terminal.

In this case, the determination of the initial phase (for a data symbolor DM-RS symbol) may occur in unit of each resource unit, and mayinclude a set unit of a frame, subframe, slot, etc. smaller than theunit of each resource unit.

Furthermore, the cycle in which the initial phase is determined may bedetermined based on the length of a DM-RS sequence, and may be used tonewly align a phase rotation after the section in which the transmissionof a signal is not performed for a specific time, such as a symbol unitor subframe unit, due to the influence of puncturing duringtransmission, blocking, etc.

Furthermore, a method of providing notification of the initial phaseagain may be used when retransmission starts after UL transmission isstopped in TDD.

Furthermore, information of the initial phase may be used as informationfor performing inter-cell interference randomization.

If a terminal transmits a DMRS through DM-RS symbols using the sametone, same DM-RS sequence as neighboring cells, interference may occur.

In order to avoid such interference, there may be an effect in thatinter-cell interference is randomized by making different a phaserotation degree (or value) of a DM-RS used in each cell.

However, if only the constellation points of DM-RS symbols are randomlyrotated, there is a problem in that a PAPR/CM between neighboring datasymbols increases.

Accordingly, in order to solve the problem, in a method of adjusting aninitial phase, the phase rotation degree (or quantity) of all ofsubframes can be resultantly adjusted.

That is, the method of adjusting an initial phase proposed in thisspecification proposes a method for each terminal to randomly generateits own initial phase based on its own cell ID in each cycle in whichthe initial phase is set again.

In this case, the random generation of the initial phase of eachterminal may be determined through a slot, subframe, frame index, etc.in addition to a cell ID.

Furthermore, a base station may notify a terminal of a value (orparameter) to determine an initial phase through RRC signaling.

As described above, a method of changing an initial phase value everytiming reset using the cycle in which an initial phase is reset has thesame effect as that cover code is used in order to solve theaforementioned problem.

Fourth Embodiment: Sequence Timing Offset Compensation Method

One method for removing accurate estimation of a DM-RS sequence andinterference is to use orthogonal sequence series, such as a Walshsequence.

However, such sequences have a disadvantage in that performance thereofcannot be guaranteed if the start point is not accurately synchronized.

For example, if different terminals use the same sequence between twocells, but the sequences are dislocated in some slot unit because theyhave different start timing, great inter-cell interference acts due to alow cross correlation property.

In order to solve this problem, if the start point of a sequence isdislocated in unit of a slot or more, a method of maintaining anorthogonal property between the sequences of two terminals bycompensating for a start point difference between the sequences may beused.

A base station may determine the reference start point of a sequencethrough the exchange of information with a neighboring cell or anadjacent base station, and may notify terminals of the correspondingstart point through signaling.

Each of the terminals that has received the start point may identify howmany slots timing when its transmission starts deviates from thereference start point of a sequence (i.e., identify a sequence timingoffset), and may use a DM-RS sequence of a time-shifted version in orderto compensate for the corresponding difference (or offset).

To this end, the base station notifies the terminals of the referencestart point of a sequence through an RRC signaling message or downlinkcontrol information.

Such a method of compensating for a sequence timing offset may be usedif a sequence of another form is used in addition to an orthogonalsequence form.

FIG. 39 is a flowchart illustrating an example of a method oftransmitting and receiving DM-RSs in NB-IoT proposed in thisspecification.

First, a terminal generates a reference signal sequence used fordemodulation with respect to single tone transmission (S3910).

Thereafter, the terminal maps the reference signal sequence to multiplesymbols (S3920).

In this case, the reference signal sequence is mapped in the order thatthe first subcarrier index k increases, in the order that a next symbolindex increases, in the order that a next slot index increases, as in aresource element mapping method of an uplink shared channel.

Thereafter, the terminal transmits a DMRS to a base station in themultiple symbols or through the multiple symbols using a single tone(S3930).

The DMRS means a reference signal used for the demodulation of a narrowband (NB) physical uplink channel, and may be called an NB DMRS.

The NB physical uplink channel may transmit at least one of uplink dataand control information.

If the NB physical uplink channel is transmitted as a single tonesupported in NB-IoT, binary phase shift keying (BPSK) or quadraturephase shift keying (QPSK) is applied to a modulation scheme for the NBphysical uplink channel.

Furthermore, the multiple symbols are symbols corresponding to the firstsymbol, second symbol and third symbol of a slot, respectively. A phaserotation is applied to each of the multiple symbols by taking intoconsideration a modulation scheme applied to the NB physical uplinkchannel.

In this case, the phase rotation may be determined based on a firstparameter determined according to the modulation scheme (BPSK or QPSK).

In this case, the first parameter may be π/2 or π/4.

Furthermore, the phase rotation may be determined based on the firstparameter and a result value obtained by performing modulo operation of2 on a symbol index indicative of a symbol within a specific time unit.

The equations described in the method 1 and method 4 of the secondembodiment may be applied to a detailed equation therefor.

Furthermore, the phase rotation may also be applied to each of datasymbols to which the NB physical uplink channel is mapped in addition tothe multiple symbols (DMRS symbols).

Furthermore, the DMRS sequence may be generated using a pseudo-randomsequence, etc.

The pseudo random sequence may be expressed as a pseudo random noise(PN) sequence.

Additionally, the terminal may apply orthogonal cover code (OCC) to themultiple symbols.

The corresponding step may be performed after step S3910 or after stepS3920.

Furthermore, the initial phase value of the phase rotation may beapplied at the start of each specific unit.

In this case, the specific unit may be a slot, a subframe, a radioframe, etc.

The initial phase value may be set using at least one of a cellidentifier (ID) and the specific unit.

The terminal transmits the DMRS to the base station through a narrowband (NB). The NB has a bandwidth of 180 kHz.

Furthermore, the terminal may transmit the DMRS in the inband mode ofthe aforementioned operation modes (or operation systems) of NB-IoT.

General Apparatus to which the Present Invention May be Applied

FIG. 40 shows an example of the internal block diagram of a wirelesscommunication apparatus to which the methods proposed in thisspecification may be applied.

Referring to FIG. 40, a wireless communication system includes an eNB4010 and multiple UEs 4020 located within the area of the eNB 4010.

The eNB 4010 includes a processor 4011, memory 4012 and a radiofrequency (RF) unit 4013. The processor 4011 implements the functions,processes and/or methods proposed in FIGS. 1 to 39. The layers of aradio interface protocol may be implemented by the processor 4011. Thememory 4012 is connected to the processor 4011 and stores various typesof information for driving the processor 4011. The RF unit 4013 isconnected to the processor 4011 and transmits and/or receives radiosignals.

The UE 4020 includes a processor 4021, memory 4022 and an RF unit 4023.The processor 4021 implements the functions, processes and/or methodsproposed FIGS. 1 to 39. The layers of a radio interface protocol may beimplemented by the processor 4021. The memory 4022 is connected to theprocessor 4021 and stores various types of information for driving theprocessor 4021. The RF unit 4023 is connected to the processor 4021 andtransmits and/or receives radio signals.

The memory 4012, 4022 may be inside or outside the processor 4011, 4021and may be connected to the processor 4011, 4021 by various well-knownmeans.

Furthermore, the eNB 4010 and/or the UE 4020 may have a single antennaor multiple antennas.

In the aforementioned embodiments, the elements and characteristics ofthe present invention have been combined in specific forms. Each of theelements or characteristics may be considered to be optional unlessotherwise described explicitly. Each of the elements or characteristicsmay be implemented in a form to be not combined with other elements orcharacteristics. Furthermore, some of the elements and/or thecharacteristics may be combined to form an embodiment of the presentinvention. Order of the operations described in the embodiments of thepresent invention may be changed. Some of the elements orcharacteristics of an embodiment may be included in another embodimentor may be replaced with corresponding elements or characteristics ofanother embodiment. It is evident that an embodiment may be constructedby combining claims not having an explicit citation relation in theclaims or may be included as a new claim by amendments after filing anapplication.

The embodiment according to the present invention may be implemented byvarious means, for example, hardware, firmware, software or acombination of them. In the case of an implementation by hardware, theembodiment of the present invention may be implemented using one or moreapplication-specific integrated circuits (ASICs), digital signalprocessors (DSPs), digital signal processing devices (DSPDs),programmable logic devices (PLDs), field programmable gate arrays(FPGAs), processors, controllers, microcontrollers, microprocessors,etc.

In the case of an implementation by firmware or software, the embodimentof the present invention may be implemented in the form of a module,procedure or function for performing the aforementioned functions oroperations. Software code may be stored in the memory and driven by theprocessor. The memory may be located inside or outside the processor andmay exchange data with the processor through a variety of known means.

It is evident to those skilled in the art that the present invention maybe materialized in other specific forms without departing from theessential characteristics of the present invention. Accordingly, thedetailed description should not be construed as being limitative, butshould be construed as being illustrative from all aspects. The scope ofthe present invention should be determined by reasonable analysis of theattached claims, and all changes within the equivalent range of thepresent invention are included in the scope of the present invention.

INDUSTRIAL APPLICABILITY

The method for transmitting a DMRS in a wireless communication systemsupporting NB-IoT of this specification has been described based on anexample in which it is applied to the 3GPP LTE/LTE-A systems, but may beapplied to various wireless communication systems, such as a 5G system,in addition to the 3GPP LTE/LTE-A systems.

1. A method of transmitting, by a terminal, a demodulation reference signal (DMRS) in a wireless communication system supporting Narrowband (NB)-Internet of Things (IoT), the method comprising: generating a reference signal sequence used a demodulation for a single tone transmission; mapping the reference signal sequence to multiple symbols; and transmitting, to a base station, the DMRS in the multiple symbols using a single tone, wherein if a narrow band (NB) physical uplink channel is transmitted as the single tone, a binary phase shift keying (BPSK) or a quadrature phase shift keying (QPSK) is applied as a modulation scheme for the NB physical uplink channel, wherein a phase rotation is applied to each of the multiple symbols, wherein the applied phase rotation is determined based on a modulation scheme applied to the NB physical uplink channel, and wherein the multiple symbols correspond to a first symbol, second symbol and third symbol of a slot, respectively.
 2. The method of claim 1, wherein the applied phase rotation is determined based on a first parameter determined according to the modulation scheme.
 3. The method of claim 2, wherein the first parameter is π/2 or π/4.
 4. The method of claim 3, wherein the applied phase rotation is determined based on the first parameter and a result value of modulo operation of 2 for a symbol index indicating a symbol within a specific time unit.
 5. The method of claim 1, wherein the phase rotation is applied to each of symbols to which the NB physical uplink channel is mapped.
 6. The method of claim 1, wherein the DMRS sequence is generated using a pseudo-random sequence.
 7. The method of claim 1, further comprising: applying an orthogonal cover code (OCC) to the multiple symbols.
 8. The method of claim 5, wherein an initial phase value of the phase rotation is applied at a start of each specific unit.
 9. The method of claim 8, wherein the specific unit is a slot, subframe or radio frame.
 10. The method of claim 8, wherein the initial phase value is set using at least one of a cell ID or the specific unit.
 11. The method of claim 1, wherein the narrow band (NB) has a bandwidth of 180 kHz.
 12. The method of claim 1, wherein the transmission of the DMRS is performed in an inband mode of the NB-IoT system.
 13. A terminal for transmitting a demodulation reference signal (DMRS) in a wireless communication system supporting Narrowband (NB)-Internet of Things (IoT), the terminal comprising: a radio frequency (RF) unit for transmitting and receiving radio signals; and a processor functionally coupled to the RF unit, wherein the processor is configured to: generate a reference signal sequence used a demodulation for a single tone transmission, map the reference signal sequence to multiple symbols, and transmit, to a base station, the DMRS in the multiple symbols using a single tone, wherein if a narrow band (NB) physical uplink channel is transmitted as the single tone, a binary phase shift keying (BPSK) or a quadrature phase shift keying (QPSK) is applied as a modulation scheme for the NB physical uplink channel, wherein a phase rotation is applied to each of the multiple symbols, wherein the applied phase rotation is determined based on a modulation scheme applied to the NB physical uplink channel, and wherein the multiple symbols correspond to a first symbol, second symbol and third symbol of a slot, respectively. 